Method and apparatus including an antenna comprising a lens and a body coupled to a feedline having a structure that reduces reflections of electromagnetic waves

ABSTRACT

Aspects of the subject disclosure may include, for example, antenna structure that includes a dielectric antenna having a dielectric lens and a dielectric body, and a feedline coupled to the dielectric antenna, wherein an endpoint of the feedline is configured to reduce a reflection of an electromagnetic wave transmission, wherein electromagnetic waves generated by the electromagnetic wave transmission are guided along the feedline without requiring an electrical return path, and wherein the electromagnetic waves propagate through the dielectric body to the dielectric lens to generate wireless signals. Other embodiments are disclosed.

CROSS-REFERENCE TO RELATED APPLICATION(S)

This application is a continuation-in-part of U.S. application Ser. No.15/486,855, filed Apr. 13, 2017 (now U.S. Pat. No. 9,882,608), which isa continuation of U.S. application Ser. No. 14/885,463, filed Oct. 16,2015 (now U.S. Pat. No. 9,722,318), which is a continuation-in-part ofU.S. application Ser. No. 14/799,272, filed Jul. 14, 2015 (now U.S. Pat.No. 9,628,116). All sections of the aforementioned applications areincorporated herein by reference in their entirety.

FIELD OF THE DISCLOSURE

The subject disclosure relates to method and apparatus for coupling toan antenna.

BACKGROUND

As smart phones and other portable devices increasingly becomeubiquitous, and data usage increases, macrocell base station devices andexisting wireless infrastructure in turn require higher bandwidthcapability in order to address the increased demand. To provideadditional mobile bandwidth, small cell deployment is being pursued,with microcells and picocells providing coverage for much smaller areasthan traditional macrocells.

In addition, most homes and businesses have grown to rely on broadbanddata access for services such as voice, video and Internet browsing,etc. Broadband access networks include satellite, 4G or 5G wireless,power line communication, fiber, cable, and telephone networks.

BRIEF DESCRIPTION OF THE DRAWINGS

Reference will now be made to the accompanying drawings, which are notnecessarily drawn to scale, and wherein:

FIG. 1 is a block diagram illustrating an example, non-limitingembodiment of a guided-wave communications system in accordance withvarious aspects described herein.

FIG. 2 is a block diagram illustrating an example, non-limitingembodiment of a transmission device in accordance with various aspectsdescribed herein.

FIG. 3 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 4 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 5A is a graphical diagram illustrating an example, non-limitingembodiment of a frequency response in accordance with various aspectsdescribed herein.

FIG. 5B is a graphical diagram illustrating example, non-limitingembodiments of a longitudinal cross-section of an insulated wiredepicting fields of guided electromagnetic waves at various operatingfrequencies in accordance with various aspects described herein.

FIG. 6 is a graphical diagram illustrating an example, non-limitingembodiment of an electromagnetic field distribution in accordance withvarious aspects described herein.

FIG. 7 is a block diagram illustrating an example, non-limitingembodiment of an arc coupler in accordance with various aspectsdescribed herein.

FIG. 8 is a block diagram illustrating an example, non-limitingembodiment of an arc coupler in accordance with various aspectsdescribed herein.

FIG. 9A is a block diagram illustrating an example, non-limitingembodiment of a stub coupler in accordance with various aspectsdescribed herein.

FIG. 9B is a diagram illustrating an example, non-limiting embodiment ofan electromagnetic distribution in accordance with various aspectsdescribed herein.

FIGS. 10A and 10B are block diagrams illustrating example, non-limitingembodiments of couplers and transceivers in accordance with variousaspects described herein.

FIG. 11 is a block diagram illustrating an example, non-limitingembodiment of a dual stub coupler in accordance with various aspectsdescribed herein.

FIG. 12 is a block diagram illustrating an example, non-limitingembodiment of a repeater system in accordance with various aspectsdescribed herein.

FIG. 13 illustrates a block diagram illustrating an example,non-limiting embodiment of a bidirectional repeater in accordance withvarious aspects described herein.

FIG. 14 is a block diagram illustrating an example, non-limitingembodiment of a waveguide system in accordance with various aspectsdescribed herein.

FIG. 15 is a block diagram illustrating an example, non-limitingembodiment of a guided-wave communications system in accordance withvarious aspects described herein.

FIGS. 16A & 16B are block diagrams illustrating an example, non-limitingembodiment of a system for managing a power grid communication system inaccordance with various aspects described herein.

FIG. 17A illustrates a flow diagram of an example, non-limitingembodiment of a method for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.

FIG. 17B illustrates a flow diagram of an example, non-limitingembodiment of a method for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.

FIGS. 18A, 18B, and 18C are block diagrams illustrating example,non-limiting embodiment of a transmission medium for propagating guidedelectromagnetic waves.

FIG. 18D is a block diagram illustrating an example, non-limitingembodiment of bundled transmission media in accordance with variousaspects described herein.

FIG. 18E is a block diagram illustrating an example, non-limitingembodiment of a plot depicting cross-talk between first and secondtransmission mediums of the bundled transmission media of FIG. 18D inaccordance with various aspects described herein.

FIG. 18F is a block diagram illustrating an example, non-limitingembodiment of bundled transmission media to mitigate cross-talk inaccordance with various aspects described herein.

FIGS. 18G and 18H are block diagrams illustrating example, non-limitingembodiments of a transmission medium with an inner waveguide inaccordance with various aspects described herein.

FIGS. 18I and 18J are block diagrams illustrating example, non-limitingembodiments of connector configurations that can be used with thetransmission medium of FIG. 18A, 18B, or 18C.

FIG. 18K is a block diagram illustrating example, non-limitingembodiments of transmission mediums for propagating guidedelectromagnetic waves.

FIG. 18L is a block diagram illustrating example, non-limitingembodiments of bundled transmission media to mitigate cross-talk inaccordance with various aspects described herein.

FIG. 18M is a block diagram illustrating an example, non-limitingembodiment of exposed stubs from the bundled transmission media for useas antennas in accordance with various aspects described herein.

FIGS. 18N, 18O, 18P, 18Q, 18R, 18S, 18T, 18U, 18V and 18W are blockdiagrams illustrating example, non-limiting embodiments of a waveguidedevice for transmitting or receiving electromagnetic waves in accordancewith various aspects described herein.

FIGS. 19A and 19B are block diagrams illustrating example, non-limitingembodiments of a dielectric antenna and corresponding gain and fieldintensity plots in accordance with various aspects described herein.

FIGS. 19C and 19D are block diagrams illustrating example, non-limitingembodiments of a dielectric antenna coupled to a lens and correspondinggain and field intensity plots in accordance with various aspectsdescribed herein.

FIGS. 19E and 19F are block diagrams illustrating example, non-limitingembodiments of a dielectric antenna coupled to a lens with ridges andcorresponding gain and field intensity plots in accordance with variousaspects described herein.

FIG. 19G is a block diagram illustrating an example, non-limitingembodiment of a dielectric antenna having an elliptical structure inaccordance with various aspects described herein.

FIG. 19H is a block diagram illustrating an example, non-limitingembodiment of near-field and far-field signals emitted by the dielectricantenna of FIG. 19G in accordance with various aspects described herein.

FIG. 19I is a block diagrams of example, non-limiting embodiments of adielectric antenna for adjusting far-field wireless signals inaccordance with various aspects described herein.

FIGS. 19J and 19K are block diagrams of example, non-limitingembodiments of a flange that can be coupled to a dielectric antenna inaccordance with various aspects described herein.

FIG. 19L1 is a block diagram of example, non-limiting embodiments of theflange, waveguide and dielectric antenna assembly in accordance withvarious aspects described herein.

FIGS. 19L2 and 19L3 are block diagrams illustrating example,non-limiting embodiments of connector configurations that can be usedwith a transmission medium in accordance with various aspects describedherein.

FIG. 19L4 illustrates a flow diagram of, an example, non-limitingembodiment of a method for transmitting signals in accordance withvarious aspects described herein.

FIG. 19L5 illustrates a flow diagram of, an example, non-limitingembodiment of a method for receiving signals in accordance with variousaspects described herein.

FIG. 19M is a block diagram of an example, non-limiting embodiment of adielectric antenna coupled to a gimbal for directing wireless signalsgenerated by the dielectric antenna in accordance with various aspectsdescribed herein.

FIG. 19N is a block diagram of an example, non-limiting embodiment of adielectric antenna in accordance with various aspects described herein.

FIG. 19O is a block diagram of an example, non-limiting embodiment of anarray of dielectric antennas configurable for steering wireless signalsin accordance with various aspects described herein.

FIGS. 20A and 20B are block diagrams illustrating example, non-limitingembodiments of the transmission medium of FIG. 18A used for inducingguided electromagnetic waves on power lines supported by utility poles.

FIG. 20C is a block diagram of an example, non-limiting embodiment of acommunication network in accordance with various aspects describedherein.

FIG. 20D is a block diagram of an example, non-limiting embodiment of anantenna mount for use in a communication network in accordance withvarious aspects described herein.

FIG. 20E is a block diagram of an example, non-limiting embodiment of anantenna mount for use in a communication network in accordance withvarious aspects described herein.

FIG. 20F is a block diagram of an example, non-limiting embodiment of anantenna mount for use in a communication network in accordance withvarious aspects described herein.

FIG. 21A illustrates a flow diagram of an example, non-limitingembodiment of a method for transmitting downlink signals.

FIG. 21B illustrates a flow diagram of an example, non-limitingembodiment of a method for transmitting uplink signals.

FIG. 21C illustrates a flow diagram of an example, non-limitingembodiment of a method for inducing and receiving electromagnetic waveson a transmission medium.

FIG. 21D illustrates a flow diagram of an example, non-limitingembodiment of a method for inducing and receiving electromagnetic waveson a transmission medium.

FIG. 21E illustrates a flow diagram of an example, non-limitingembodiment of a method for transmitting wireless signals from adielectric antenna.

FIG. 21F illustrates a flow diagram of an example, non-limitingembodiment of a method for receiving wireless signals at a dielectricantenna.

FIG. 21G illustrates a flow diagram of an example, non-limitingembodiment of a method for detecting and mitigating disturbancesoccurring in a communication network.

FIG. 21H is a block diagram illustrating an example, non-limitingembodiment of an alignment of fields of an electromagnetic wave tomitigate propagation losses due to water accumulation on a transmissionmedium in accordance with various aspects described herein.

FIGS. 21I and 21J are block diagrams illustrating example, non-limitingembodiments of electric field intensities of different electromagneticwaves propagating in the cable illustrated in FIG. 20H in accordancewith various aspects described herein.

FIG. 21K is a block diagram illustrating an example, non-limitingembodiment of electric fields of a Goubau wave in accordance withvarious aspects described herein.

FIG. 21L is a block diagram illustrating an example, non-limitingembodiment of electric fields of a hybrid wave in accordance withvarious aspects described herein.

FIG. 21M is a block diagram illustrating an example, non-limitingembodiment of electric field characteristics of a hybrid wave versus aGoubau wave in accordance with various aspects described herein.

FIG. 21N is a block diagram illustrating an example, non-limitingembodiment of mode sizes of hybrid waves at various operatingfrequencies in accordance with various aspects described herein.

FIGS. 22A and 22B are block diagrams illustrating example, non-limitingembodiments of a waveguide device for launching hybrid waves inaccordance with various aspects described herein.

FIGS. 23A, 23B, and 23C are block diagrams illustrating example,non-limiting embodiments of a waveguide device in accordance withvarious aspects described herein.

FIG. 24 is a block diagram illustrating an example, non-limitingembodiment of a waveguide device in accordance with various aspectsdescribed herein.

FIG. 25A is a block diagram illustrating an example, non-limitingembodiment of a waveguide device in accordance with various aspectsdescribed herein.

FIGS. 25B, 25C and 25D are block diagrams illustrating example,non-limiting embodiments of wave modes and electric field plots inaccordance with various aspects described herein.

FIG. 26 illustrates a flow diagram of an example, non-limitingembodiment of a method for managing electromagnetic waves.

FIG. 27 is a block diagram illustrating an example, non-limitingembodiment of substantially orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 28 is a block diagram illustrating an example, non-limitingembodiment of an insulated conductor in accordance with various aspectsdescribed herein.

FIG. 29 is a block diagram illustrating an example, non-limitingembodiment of an uninsulated conductor in accordance with variousaspects described herein.

FIG. 30 is a block diagram illustrating an example, non-limitingembodiment of an oxide layer formed on the uninsulated conductor of FIG.25A in accordance with various aspects described herein.

FIG. 31 is a block diagram illustrating example, non-limitingembodiments of spectral plots in accordance with various aspectsdescribed herein.

FIG. 32 is a block diagram illustrating example, non-limitingembodiments of spectral plots in accordance with various aspectsdescribed herein.

FIG. 33 is a block diagram illustrating example, non-limitingembodiments for transmitting orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 34 is a block diagram illustrating example, non-limitingembodiments for transmitting orthogonal wave modes in accordance withvarious aspects described herein.

FIG. 35 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 36 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 37 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 38 is a block diagram illustrating example, non-limitingembodiments for selectively receiving a wave mode in accordance withvarious aspects described herein.

FIG. 39 is a block diagram illustrating example, non-limitingembodiments of a polyrod antenna for transmitting wireless signals inaccordance with various aspects described herein.

FIG. 40 is a block diagram illustrating an example, non-limitingembodiment of electric field characteristics of transmitted signals froma polyrod antenna in accordance with various aspects described herein.

FIGS. 41 and 42 are block diagrams illustrating an example, non-limitingembodiment of a polyrod antenna array in accordance with various aspectsdescribed herein.

FIGS. 43A, and 43B are block diagrams illustrating an example,non-limiting embodiment of an antenna, and electric fieldcharacteristics of transmitted signals from the antenna in accordancewith various aspects described herein.

FIG. 44A is a block diagram illustrating an example, non-limitingembodiment of a communication system in accordance with various aspectsdescribed herein.

FIG. 44B is a block diagram illustrating an example, non-limitingembodiment of a portion of the communication system of FIG. 44A inaccordance with various aspects described herein.

FIG. 44C is a graphical diagram illustrating an example, non-limitingembodiment of downlink and uplink communication techniques for enablinga base station to communicate with communication nodes in accordancewith various aspects described herein.

FIG. 44D is a graphical diagram illustrating an example, non-limitingembodiment of a frequency spectrum in accordance with various aspectsdescribed herein.

FIG. 44E is a graphical diagram illustrating an example, non-limitingembodiment of a frequency spectrum in accordance with various aspectsdescribed herein.

FIG. 45 is a block diagram illustrating an example, non-limitingembodiment of a communication system that utilizes beam steering inaccordance with various aspects described herein.

FIG. 46 is a block diagram of an example, non-limiting embodiment of acomputing environment in accordance with various aspects describedherein.

FIG. 47 is a block diagram of an example, non-limiting embodiment of amobile network platform in accordance with various aspects describedherein.

FIG. 48 is a block diagram of an example, non-limiting embodiment of acommunication device in accordance with various aspects describedherein.

DETAILED DESCRIPTION

One or more embodiments are now described with reference to thedrawings, wherein like reference numerals are used to refer to likeelements throughout the drawings. In the following description, forpurposes of explanation, numerous details are set forth in order toprovide a thorough understanding of the various embodiments. It isevident, however, that the various embodiments can be practiced withoutthese details (and without applying to any particular networkedenvironment or standard).

In an embodiment, a guided wave communication system is presented forsending and receiving communication signals such as data or othersignaling via guided electromagnetic waves. The guided electromagneticwaves include, for example, surface waves or other electromagnetic wavesthat are bound to or guided by a transmission medium as describedherein. It will be appreciated that a variety of transmission media canbe utilized with guided wave communications without departing fromexample embodiments. Examples of such transmission media can include oneor more of the following, either alone or in one or more combinations:wires, whether insulated or not, and whether single-stranded ormulti-stranded; conductors of other shapes or configurations includingunshielded twisted pair cables including single twisted pairs, Category5e and other twisted pair cable bundles, other wire bundles, cables,rods, rails, pipes; non-conductors such as dielectric pipes, rods,rails, or other dielectric members; combinations of conductors anddielectric materials; or other guided wave transmission media.

The inducement of guided electromagnetic waves that propagate along atransmission medium can be independent of any electrical potential,charge or current that is injected or otherwise transmitted through thetransmission medium as part of an electrical circuit. For example, inthe case where the transmission medium is a wire, it is to beappreciated that while a small current in the wire may be formed inresponse to the propagation of the electromagnetic waves guided alongthe wire, this can be due to the propagation of the electromagnetic wavealong the wire surface, and is not formed in response to electricalpotential, charge or current that is injected into the wire as part ofan electrical circuit. The electromagnetic waves traveling along thewire therefore do not require an electrical circuit (i.e., ground oranother electrical return path) to propagate along the wire surface. Thewire therefore is a single wire transmission line that is not part of anelectrical circuit. For example, electromagnetic waves can propagatealong a wire configured as an electrical open circuit. Also, in someembodiments, a wire is not necessary, and the electromagnetic waves canpropagate along a single line transmission medium that is not a wireincluding a single line transmission medium that is conductorless.

More generally, “guided electromagnetic waves” or “guided waves” asdescribed by the subject disclosure are affected by the presence of aphysical object that is at least a part of the transmission medium(e.g., a bare wire or other conductor, a dielectric including adielectric core without a conductive shield and/or without an innerconductor, an insulated wire, a conduit or other hollow element whetherconductive or not, a bundle of insulated wires that is coated, coveredor surrounded by a dielectric or insulator or other wire bundle, oranother form of solid, liquid or otherwise non-gaseous transmissionmedium) so as to be at least partially bound to or guided by thephysical object and so as to propagate along a transmission path of thephysical object. Such a physical object can operate as at least a partof a transmission medium that guides, by way of one or more interfacesof the transmission medium (e.g., an outer surface, inner surface, aninterior portion between the outer and the inner surfaces or otherboundary between elements of the transmission medium). In this fashion,a transmission medium may support multiple transmission paths overdifferent surfaces of the transmission medium. For example, a strandedcable or wire bundle may support electromagnetic waves that are guidedby the outer surface of the stranded cable or wire bundle, as well aselectromagnetic waves that are guided by inner cable surfaces betweentwo, three or more individual strands or wires within the stranded cableor wire bundle. For example, electromagnetic waves can be guided withininterstitial areas of a stranded cable, insulated twisted pair wires, ora wire bundle. The guided electromagnetic waves of the subjectdisclosure are launched from a sending (transmitting) device andpropagate along the transmission medium for reception by at least onereceiving device. The propagation of guided electromagnetic waves, cancarry energy, data and/or other signals along the transmission path fromthe sending device to the receiving device.

As used herein the term “conductor” (based on a definition of the term“conductor” from IEEE 100, the Authoritative Dictionary of IEEEStandards Terms, 7^(th) Edition, 2000) means a substance or body thatallows a current of electricity to pass continuously along it. The terms“insulator”, “conductorless” or “nonconductor” (based on a definition ofthe term “insulator” from IEEE 100, the Authoritative Dictionary of IEEEStandards Terms, 7^(th) Edition, 2000) means a device or material inwhich electrons or ions cannot be moved easily. It is possible for aninsulator, or a conductorless or nonconductive material to be intermixedintentionally (e.g., doped) or unintentionally into a resultingsubstance with a small amount of another material having the propertiesof a conductor. However, the resulting substance may remainsubstantially resistant to a flow of a continuous electrical currentalong the resulting substance. Furthermore, a conductorless member suchas a dielectric rod or other conductorless core lacks an inner conductorand a conductive shield. As used herein, the term “eddy current” (basedon a definition of the term “conductor” from IEEE 100, the AuthoritativeDictionary of IEEE Standards Terms, 7^(th) Edition, 2000) means acurrent that circulates in a metallic material as a result ofelectromotive forces induced by a variation of magnetic flux. Althoughit may be possible for an insulator, conductorless or nonconductivematerial in the foregoing embodiments to allow eddy currents thatcirculate within the doped or intermixed conductor and/or a very smallcontinuous flow of an electrical current along the extent of theinsulator, conductorless or nonconductive material, any such continuousflow of electrical current along such an insulator, conductorless ornonconductive material is de minimis compared to the flow of anelectrical current along a conductor. Accordingly, in the subjectdisclosure an insulator, and a conductorless or nonconductor materialare not considered to be a conductor. The term “dielectric” means aninsulator that can be polarized by an applied electric field. When adielectric is placed in an electric field, electric charges do notcontinuously flow through the material as they do in a conductor, butonly slightly shift from their average equilibrium positions causingdielectric polarization. The terms “conductorless transmission medium ornon-conductor transmission medium” can mean a transmission mediumconsisting of any material (or combination of materials) that may or maynot contain one or more conductive elements but lacks a continuousconductor between the sending and receiving devices along theconductorless transmission medium or non-conductor transmissionmedium—similar or identical to the aforementioned properties of aninsulator, conductorless or nonconductive material.

Unlike free space propagation of wireless signals such as unguided (orunbounded) electromagnetic waves that decrease in intensity inversely bythe square of the distance traveled by the unguided electromagneticwaves, guided electromagnetic waves can propagate along a transmissionmedium with less loss in magnitude per unit distance than experienced byunguided electromagnetic waves.

Unlike electrical signals, guided electromagnetic waves can propagatefrom a sending device to a receiving device without requiring a separateelectrical return path between the sending device and the receivingdevice. As a consequence, guided electromagnetic waves can propagatefrom a sending device to a receiving device along a conductorlesstransmission medium including a transmission medium having no conductivecomponents (e.g., a dielectric strip, rod, or pipe), or via atransmission medium having no more than a single conductor (e.g., asingle bare wire or insulated wire configured in an open electricalcircuit). Even if a transmission medium includes one or more conductivecomponents and the guided electromagnetic waves propagating along thetransmission medium generate currents that flow in the one or moreconductive components in a direction of the guided electromagneticwaves, such guided electromagnetic waves can propagate along thetransmission medium from a sending device to a receiving device withoutrequiring a flow of opposing currents on an electrical return pathbetween the sending device and the receiving device (i.e., in anelectrical open circuit configuration).

In a non-limiting illustration, consider electrical systems thattransmit and receive electrical signals between sending and receivingdevices by way of conductive media. Such systems generally rely on anelectrical forward path and an electrical return path. For instance,consider a coaxial cable having a center conductor and a ground shieldthat are separated by an insulator. Typically, in an electrical system afirst terminal of a sending (or receiving) device can be connected tothe center conductor, and a second terminal of the sending (orreceiving) device can be connected to the ground shield or other secondconductor. If the sending device injects an electrical signal in thecenter conductor via the first terminal, the electrical signal willpropagate along the center conductor causing forward currents in thecenter conductor, and return currents in the ground shield or othersecond conductor. The same conditions apply for a two terminal receivingdevice.

In contrast, consider a guided wave communication system such asdescribed in the subject disclosure, which can utilize differentembodiments of a transmission medium (including among others a coaxialcable) for transmitting and receiving guided electromagnetic waveswithout requiring an electrical return path. In one embodiment, forexample, the guided wave communication system of the subject disclosurecan be configured to induce guided electromagnetic waves that propagatealong an outer surface of a coaxial cable. Although the guidedelectromagnetic waves can cause forward currents on the ground shield,the guided electromagnetic waves do not require return currents on, forexample, the center conductor to enable the guided electromagnetic wavesto propagate along the outer surface of the coaxial cable. The same canbe said of other transmission media used by a guided wave communicationsystem for the transmission and reception of guided electromagneticwaves. For example, guided electromagnetic waves induced by the guidedwave communication system on a bare wire, an insulated wire, or adielectric transmission medium (e.g., a dielectric core with noconductive materials), can propagate along the bare wire, the insulatedbare wire, or the dielectric transmission medium without requiringreturn currents on an electrical return path.

Consequently, electrical systems that require forward and returnconductors for carrying corresponding forward and reverse currents onconductors to enable the propagation of electrical signals injected by asending device are distinct from guided wave systems that induce guidedelectromagnetic waves on an interface of a transmission medium withoutrequiring an electrical return path to enable the propagation of theguided electromagnetic waves along the interface of the transmissionmedium.

It is further noted that guided electromagnetic waves as described inthe subject disclosure can have an electromagnetic field structure thatlies primarily or substantially on an outer surface of a transmissionmedium so as to be bound to or guided by the outer surface of thetransmission medium and so as to propagate non-trivial distances on oralong the outer surface of the transmission medium. In otherembodiments, guided electromagnetic waves can have an electromagneticfield structure that lies primarily or substantially below an outersurface of a transmission medium so as to be bound to or guided by aninner material of the transmission medium (e.g., dielectric material)and so as to propagate non-trivial distances within the inner materialof the transmission medium. In other embodiments, guided electromagneticwaves can have an electromagnetic field structure that lies within aregion that is partially below and partially above an outer surface of atransmission medium so as to be bound to or guided by this region of thetransmission medium and so as to propagate non-trivial distances alongthis region of the transmission medium. The desired electromagneticfield structure in an embodiment may vary based upon a variety offactors, including the desired transmission distance, thecharacteristics of the transmission medium itself, and environmentalconditions/characteristics outside of the transmission medium (e.g.,presence of rain, fog, atmospheric conditions, etc.).

Various embodiments described herein relate to coupling devices, thatcan be referred to as “waveguide coupling devices”, “waveguide couplers”or more simply as “couplers”, “coupling devices” or “launchers” forlaunching and/or receiving/extracting guided electromagnetic waves toand from a transmission medium, wherein a wavelength of the guidedelectromagnetic waves can be small compared to one or more dimensions ofthe coupling device and/or the transmission medium such as thecircumference of a wire or other cross sectional dimension. Suchelectromagnetic waves can operate at millimeter wave frequencies (e.g.,30 to 300 GHz), or lower than microwave frequencies such as 300 MHz to30 GHz. Electromagnetic waves can be induced to propagate along atransmission medium by a coupling device, such as: a strip, arc or otherlength of dielectric material; a millimeter wave integrated circuit(MMIC), a horn, monopole, rod, slot or other antenna; an array ofantennas; a magnetic resonant cavity or other resonant coupler; a coil,a strip line, a coaxial waveguide or other waveguide and/or othercoupling device. In operation, the coupling device receives anelectromagnetic wave from a transmitter or transmission medium. Theelectromagnetic field structure of the electromagnetic wave can becarried below an outer surface of the coupling device, substantially onthe outer surface of the coupling device, or a combination thereof. Whenthe coupling device is in close proximity to a transmission medium, atleast a portion of an electromagnetic wave couples to or is bound to thetransmission medium, and continues to propagate as guidedelectromagnetic waves along the transmission medium. In a reciprocalfashion, a coupling device can receive or extract at least a portion ofthe guided electromagnetic waves from a transmission medium and transferthese electromagnetic waves to a receiver. The guided electromagneticwaves launched and/or received by the coupling device propagate alongthe transmission medium from a sending device to a receiving devicewithout requiring an electrical return path between the sending deviceand the receiving device. In this circumstance, the transmission mediumacts as a waveguide to support the propagation of the guidedelectromagnetic waves from the sending device to the receiving device.

According to an example embodiment, a surface wave is a type of guidedwave that is guided by a surface of a transmission medium, such as anexterior or outer surface or an interior or inner surface including aninterstitial surface of the transmission medium such as the interstitialarea between wires in a multistranded cable, insulated twisted pairwires, or wire bundle, and/or another surface of the transmission mediumthat is adjacent to or exposed to another type of medium havingdifferent properties (e.g., dielectric properties). Indeed, in anexample embodiment, a surface of the transmission medium that guides asurface wave can represent a transitional surface between two differenttypes of media. For example, in the case of a bare wire or uninsulatedwire, the surface of the wire can be the outer or exterior conductivesurface of the bare wire or uninsulated wire that is exposed to air orfree space. As another example, in the case of insulated wire, thesurface of the wire can be the conductive portion of the wire that meetsan inner surface of the insulator portion of the wire. A surface of thetransmission medium can be any one of an inner surface of an insulatorsurface of a wire or a conductive surface of the wire that is separatedby a gap composed of, for example, air or free space. A surface of atransmission medium can otherwise be any material region of thetransmission medium. For example, the surface of the transmission mediumcan be an inner portion of an insulator disposed on a conductive portionof the wire that meets the insulator portion of the wire. The surfacethat guides an electromagnetic wave can depend upon the relativedifferences in the properties (e.g., dielectric properties) of theinsulator, air, and/or the conductor and further dependent on thefrequency and propagation mode or modes of the guided wave.

According to an example embodiment, the term “about” a wire or othertransmission medium used in conjunction with a guided wave can includefundamental guided wave propagation modes such as a guided waves havinga circular or substantially circular field pattern/distribution, asymmetrical electromagnetic field pattern/distribution (e.g., electricfield or magnetic field) or other fundamental mode pattern at leastpartially around a wire or other transmission medium. Unlike Zenneckwaves that propagate along a single planar surface of a planartransmission medium, the guided electromagnetic waves of the subjectdisclosure that are bound to a transmission medium can have a non-planarsurface have electromagnetic field patterns that surround orcircumscribe, at least in part, the non-planar surface of thetransmission medium with electromagnetic energy in all directions, or inall but a finite number of azimuthal null directions characterized byfield strengths that approach zero field strength for infinitesimallysmall azimuthal widths.

For example, such non-circular field distributions can be unilateral ormulti-lateral with one or more axial lobes characterized by relativelyhigher field strength and/or one or more nulls directions of zero fieldstrength or substantially zero-field strength or null regionscharacterized by relatively low-field strength, zero-field strengthand/or substantially zero-field strength. Further, the fielddistribution can otherwise vary as a function of azimuthal orientationaround a transmission medium such that one or more angular regionsaround the transmission medium have an electric or magnetic fieldstrength (or combination thereof) that is higher than one or more otherangular regions of azimuthal orientation, according to an exampleembodiment. It will be appreciated that the relative orientations orpositions of the guided wave higher order modes, particularlyasymmetrical modes, can vary as the guided wave travels along the wire.

In addition, when a guided wave propagates “about” a wire or other typeof transmission medium, it can do so according to a guided wavepropagation mode that includes not only the fundamental wave propagationmodes (e.g., zero order modes), but additionally or alternatively,non-fundamental wave propagation modes such as higher-order guided wavemodes (e.g., 1^(st) order modes, 2^(nd) order modes, etc.). Higher-ordermodes include symmetrical modes that have a circular or substantiallycircular electric or magnetic field distribution and/or a symmetricalelectric or magnetic field distribution, or asymmetrical modes and/orother guided (e.g., surface) waves that have non-circular and/orasymmetrical field distributions around the wire or other transmissionmedium. For example, the guided electromagnetic waves of the subjectdisclosure can propagate along a transmission medium from the sendingdevice to the receiving device or along a coupling device via one ormore guided wave modes such as a fundamental transverse magnetic (TM)TM00 mode (or Goubau mode), a fundamental hybrid mode (EH or HE) “EH00”mode or “HE00” mode, a transverse electromagnetic “TEMnm” mode, a totalinternal reflection (TIR) mode or any other mode such as EHnm, HEnm orTMnm, where n and/or m have integer values greater than or equal to 0,and other fundamental, hybrid and non-fundamental wave modes.

As used herein, the term “guided wave mode” refers to a guided wavepropagation mode of a transmission medium, coupling device or othersystem component of a guided wave communication system that propagatesfor non-trivial distances along the length of the transmission medium,coupling device or other system component.

As used herein, the term “millimeter-wave” can refer to electromagneticwaves/signals that fall within the “millimeter-wave frequency band” of30 GHz to 300 GHz. The term “microwave” can refer to electromagneticwaves/signals that fall within a “microwave frequency band” of 300 MHzto 300 GHz. The term “radio frequency” or “RF” can refer toelectromagnetic waves/signals that fall within the “radio frequencyband” of 10 kHz to 1 THz. It is appreciated that wireless signals,electrical signals, and guided electromagnetic waves as described in thesubject disclosure can be configured to operate at any desirablefrequency range, such as, for example, at frequencies within, above orbelow millimeter-wave and/or microwave frequency bands. In particular,when a coupling device or transmission medium includes a conductiveelement, the frequency of the guided electromagnetic waves that arecarried by the coupling device and/or propagate along the transmissionmedium can be below the mean collision frequency of the electrons in theconductive element. Further, the frequency of the guided electromagneticwaves that are carried by the coupling device and/or propagate along thetransmission medium can be a non-optical frequency, e.g., a radiofrequency below the range of optical frequencies that begins at 1 THz.

It is further appreciated that a transmission medium as described in thesubject disclosure can be configured to be opaque or otherwise resistantto (or at least substantially reduce) a propagation of electromagneticwaves operating at optical frequencies (e.g., greater than 1 THz).

As used herein, the term “antenna” can refer to a device that is part ofa transmitting or receiving system to transmit/radiate or receive freespace wireless signals.

In accordance with one or more embodiments, a communication device caninclude a dielectric antenna having a dielectric lens and a dielectricbody, and a dielectric feedline coupled to the dielectric antenna,wherein an endpoint of the dielectric feedline comprises a structurethat reduces a reflection of an electromagnetic wave transmission,wherein first electromagnetic waves generated by the electromagneticwave transmission are guided along the dielectric feedline withoutrequiring an electrical return path, and wherein the firstelectromagnetic waves propagate through the dielectric body to thedielectric lens to generate near-field wireless signals.

In accordance with one or more embodiments, antenna structure caninclude a dielectric antenna having a dielectric lens and a dielectricbody, and a feedline coupled to the dielectric antenna, wherein anendpoint of the feedline is configured to reduce a reflection of anelectromagnetic wave transmission, wherein electromagnetic wavesgenerated by the electromagnetic wave transmission are guided along thefeedline without requiring an electrical return path, and wherein theelectromagnetic waves propagate through the dielectric body to thedielectric lens to generate wireless signals.

In accordance with one or more embodiments, a method can includealigning a feedline of a dielectric antenna comprising a dielectric lensand a dielectric body with a port of a waveguide system, wherein firstelectromagnetic waves are guided along the feedline without requiring anelectrical return path, and wherein the first electromagnetic wavespropagate through the dielectric body to the dielectric lens to generatefirst wireless signals, and transmitting, by the waveguide system, thefirst electromagnetic waves that propagate along the feedline, whereinan endpoint of the feedline is configured to reduce a reflection of thefirst electromagnetic waves.

Referring now to FIG. 1, a block diagram 100 illustrating an example,non-limiting embodiment of a guided wave communications system is shown.In operation, a transmission device 101 receives one or morecommunication signals 110 from a communication network or othercommunications device that includes data and generates guided waves 120to convey the data via the transmission medium 125 to the transmissiondevice 102. The transmission device 102 receives the guided waves 120and converts them to communication signals 112 that include the data fortransmission to a communications network or other communications device.The guided waves 120 can be modulated to convey data via a modulationtechnique such as phase shift keying, frequency shift keying, quadratureamplitude modulation, amplitude modulation, multi-carrier modulationsuch as orthogonal frequency division multiplexing and via multipleaccess techniques such as frequency division multiplexing, time divisionmultiplexing, code division multiplexing, multiplexing via differingwave propagation modes and via other modulation and access strategies.

The communication network or networks can include a wirelesscommunication network such as a mobile data network, a cellular voiceand data network, a wireless local area network (e.g., WiFi or an IEEE802 series network), a satellite communications network, a personal areanetwork or other wireless network. The communication network or networkscan also include a wired communication network such as a telephonenetwork, an Ethernet network, a local area network, a wide area networksuch as the Internet, a broadband access network, a cable network, afiber optic network, or other wired network. The communication devicescan include a network edge device, bridge device or home gateway, aset-top box, broadband modem, telephone adapter, access point, basestation, or other fixed communication device, a mobile communicationdevice such as an automotive gateway or another device of an automobile,laptop computer, tablet, smartphone, cellular telephone, or othercommunication device.

In an example embodiment, the guided wave communication system 100 canoperate in a bi-directional fashion where transmission device 102receives one or more communication signals 112 from a communicationnetwork or device that includes other data and generates guided waves122 to convey the other data via the transmission medium 125 to thetransmission device 101. In this mode of operation, the transmissiondevice 101 receives the guided waves 122 and converts them tocommunication signals 110 that include the other data for transmissionto a communications network or device. The guided waves 122 can bemodulated to convey data via a modulation technique such as phase shiftkeying, frequency shift keying, quadrature amplitude modulation,amplitude modulation, multi-carrier modulation such as orthogonalfrequency division multiplexing and via multiple access techniques suchas frequency division multiplexing, time division multiplexing, codedivision multiplexing, multiplexing via differing wave propagation modesand via other modulation and access strategies.

The transmission medium 125 can include a cable having at least oneinner portion surrounded by a dielectric material such as an insulatoror other dielectric cover, coating or other dielectric material, thedielectric material having an outer surface and a correspondingcircumference. In an example embodiment, the transmission medium 125operates as a single-wire transmission line to guide the transmission ofan electromagnetic wave. When the transmission medium 125 is implementedas a single wire transmission system, it can include a wire. The wirecan be insulated or uninsulated, and single-stranded or multi-stranded(e.g., braided). In other embodiments, the transmission medium 125 cancontain conductors of other shapes or configurations including wirebundles, cables, rods, rails, pipes. In addition, the transmissionmedium 125 can include non-conductors such as dielectric pipes, rods,rails, or other dielectric members; combinations of conductors anddielectric materials, conductors without dielectric materials or otherguided wave transmission media. It should be noted that the transmissionmedium 125 can otherwise include any of the transmission mediapreviously discussed.

Further, as previously discussed, the guided waves 120 and 122 can becontrasted with radio transmissions over free space/air or conventionalpropagation of electrical power or signals through the conductor of awire via an electrical circuit. In addition to the propagation of guidedwaves 120 and 122, the transmission medium 125 may optionally containone or more wires that propagate electrical power or other communicationsignals in a conventional manner as a part of one or more electricalcircuits.

Referring now to FIG. 2, a block diagram 200 illustrating an example,non-limiting embodiment of a transmission device is shown. Thetransmission device 101 or 102 includes a communications interface (I/F)205, a transceiver 210 and a coupler 220.

In an example of operation, the communications interface 205 receives acommunication signal 110 or 112 that includes data. In variousembodiments, the communications interface 205 can include a wirelessinterface for receiving a wireless communication signal in accordancewith a wireless standard protocol such as LTE (Long Term Evolution) orother cellular voice and data protocol, WiFi (Wireless Fidelity) or an802.11 protocol, WIMAX (Worldwide Interoperability for Microwave Access)protocol, Ultra Wideband protocol, BLUETOOTH® protocol, ZIGBEE®protocol, a direct broadcast satellite (DBS) or other satellitecommunication protocol or other wireless protocol. In addition or in thealternative, the communications interface 205 includes a wired interfacethat operates in accordance with an Ethernet protocol, universal serialbus (USB) protocol, a data over cable service interface specification(DOCSIS) protocol, a digital subscriber line (DSL) protocol, a Firewire(IEEE 1394) protocol, or other wired protocol. In additional tostandards-based protocols, the communications interface 205 can operatein conjunction with other wired or wireless protocol. In addition, thecommunications interface 205 can optionally operate in conjunction witha protocol stack that includes multiple protocol layers including a MAC(media access control) protocol, transport protocol, applicationprotocol, etc.

In an example of operation, the transceiver 210 generates anelectromagnetic wave based on the communication signal 110 or 112 toconvey the data. The electromagnetic wave has at least one carrierfrequency and at least one corresponding wavelength. The carrierfrequency can be within a millimeter-wave frequency band of 30 GHz-300GHz, such as 60 GHz or a carrier frequency in the range of 30-40 GHz ora lower frequency band of 300 MHz-30 GHz in the microwave frequencyrange such as 26-30 GHz, 11 GHz, 6 GHz or 3 GHz, but it will beappreciated that other carrier frequencies are possible in otherembodiments. In one mode of operation, the transceiver 210 merelyupconverts the communications signal or signals 110 or 112 fortransmission of the electromagnetic signal in the microwave ormillimeter-wave band as a guided electromagnetic wave that is guided byor bound to the transmission medium 125. In another mode of operation,the communications interface 205 either converts the communicationsignal 110 or 112 to a baseband or near baseband signal or extracts thedata from the communication signal 110 or 112 and the transceiver 210modulates a high-frequency carrier with the data, the baseband or nearbaseband signal for transmission. It should be appreciated that thetransceiver 210 can modulate the data received via the communicationsignal 110 or 112 to preserve one or more data communication protocolsof the communication signal 110 or 112 either by encapsulation in thepayload of a different protocol or by simple frequency shifting. In thealternative, the transceiver 210 can otherwise translate the datareceived via the communication signal 110 or 112 to a protocol that isdifferent from the data communication protocol or protocols of thecommunication signal 110 or 112.

In an example of operation, the coupler 220 couples the electromagneticwave to the transmission medium 125 as a guided electromagnetic wave toconvey the communications signal or signals 110 or 112. While the priordescription has focused on the operation of the transceiver 210 as atransmitter, the transceiver 210 can also operate to receiveelectromagnetic waves that convey other data from the single wiretransmission medium via the coupler 220 and to generate communicationssignals 110 or 112, via communications interface 205 that includes theother data. Consider embodiments where an additional guidedelectromagnetic wave conveys other data that also propagates along thetransmission medium 125. The coupler 220 can also couple this additionalelectromagnetic wave from the transmission medium 125 to the transceiver210 for reception.

The transmission device 101 or 102 includes an optional trainingcontroller 230. In an example embodiment, the training controller 230 isimplemented by a standalone processor or a processor that is shared withone or more other components of the transmission device 101 or 102. Thetraining controller 230 selects the carrier frequencies, modulationschemes and/or guided wave modes for the guided electromagnetic wavesbased on feedback data received by the transceiver 210 from at least oneremote transmission device coupled to receive the guided electromagneticwave.

In an example embodiment, a guided electromagnetic wave transmitted by aremote transmission device 101 or 102 conveys data that also propagatesalong the transmission medium 125. The data from the remote transmissiondevice 101 or 102 can be generated to include the feedback data. Inoperation, the coupler 220 also couples the guided electromagnetic wavefrom the transmission medium 125 and the transceiver receives theelectromagnetic wave and processes the electromagnetic wave to extractthe feedback data.

In an example embodiment, the training controller 230 operates based onthe feedback data to evaluate a plurality of candidate frequencies,modulation schemes and/or transmission modes to select a carrierfrequency, modulation scheme and/or transmission mode to enhanceperformance, such as throughput, signal strength, reduce propagationloss, etc.

Consider the following example: a transmission device 101 beginsoperation under control of the training controller 230 by sending aplurality of guided waves as test signals such as pilot waves or othertest signals at a corresponding plurality of candidate frequenciesand/or candidate modes directed to a remote transmission device 102coupled to the transmission medium 125. The guided waves can include, inaddition or in the alternative, test data. The test data can indicatethe particular candidate frequency and/or guide-wave mode of the signal.In an embodiment, the training controller 230 at the remote transmissiondevice 102 receives the test signals and/or test data from any of theguided waves that were properly received and determines the bestcandidate frequency and/or guided wave mode, a set of acceptablecandidate frequencies and/or guided wave modes, or a rank ordering ofcandidate frequencies and/or guided wave modes. This selection ofcandidate frequenc(ies) or/and guided-mode(s) are generated by thetraining controller 230 based on one or more optimizing criteria such asreceived signal strength, bit error rate, packet error rate, signal tonoise ratio, propagation loss, etc. The training controller 230generates feedback data that indicates the selection of candidatefrequenc(ies) or/and guided wave mode(s) and sends the feedback data tothe transceiver 210 for transmission to the transmission device 101. Thetransmission device 101 and 102 can then communicate data with oneanother based on the selection of candidate frequenc(ies) or/and guidedwave mode(s).

In other embodiments, the guided electromagnetic waves that contain thetest signals and/or test data are reflected back, repeated back orotherwise looped back by the remote transmission device 102 to thetransmission device 101 for reception and analysis by the trainingcontroller 230 of the transmission device 101 that initiated thesewaves. For example, the transmission device 101 can send a signal to theremote transmission device 102 to initiate a test mode where a physicalreflector is switched on the line, a termination impedance is changed tocause reflections, a loop back mode is switched on to coupleelectromagnetic waves back to the source transmission device 102, and/ora repeater mode is enabled to amplify and retransmit the electromagneticwaves back to the source transmission device 102. The trainingcontroller 230 at the source transmission device 102 receives the testsignals and/or test data from any of the guided waves that were properlyreceived and determines selection of candidate frequenc(ies) or/andguided wave mode(s).

While the procedure above has been described in a start-up orinitialization mode of operation, each transmission device 101 or 102can send test signals, evaluate candidate frequencies or guided wavemodes via non-test such as normal transmissions or otherwise evaluatecandidate frequencies or guided wave modes at other times orcontinuously as well. In an example embodiment, the communicationprotocol between the transmission devices 101 and 102 can include anon-request or periodic test mode where either full testing or morelimited testing of a subset of candidate frequencies and guided wavemodes are tested and evaluated. In other modes of operation, there-entry into such a test mode can be triggered by a degradation ofperformance due to a disturbance, weather conditions, etc. In an exampleembodiment, the receiver bandwidth of the transceiver 210 is eithersufficiently wide or swept to receive all candidate frequencies or canbe selectively adjusted by the training controller 230 to a trainingmode where the receiver bandwidth of the transceiver 210 is sufficientlywide or swept to receive all candidate frequencies.

Referring now to FIG. 3, a graphical diagram 300 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In this embodiment, a transmission medium 125 inair includes an inner conductor 301 and an insulating jacket 302 ofdielectric material, as shown in cross section. The diagram 300 includesdifferent gray-scales that represent differing electromagnetic fieldstrengths generated by the propagation of the guided wave having anasymmetrical and non-fundamental guided wave mode.

In particular, the electromagnetic field distribution corresponds to amodal “sweet spot” that enhances guided electromagnetic wave propagationalong an insulated transmission medium and reduces end-to-endtransmission loss. In this particular mode, electromagnetic waves areguided by the transmission medium 125 to propagate along an outersurface of the transmission medium—in this case, the outer surface ofthe insulating jacket 302. Electromagnetic waves are partially embeddedin the insulator and partially radiating on the outer surface of theinsulator. In this fashion, electromagnetic waves are “lightly” coupledto the insulator so as to enable electromagnetic wave propagation atlong distances with low propagation loss.

As shown, the guided wave has a field structure that lies primarily orsubstantially outside of the transmission medium 125 that serves toguide the electromagnetic waves. The regions inside the conductor 301have little or no field. Likewise regions inside the insulating jacket302 have low field strength. The majority of the electromagnetic fieldstrength is distributed in the lobes 304 at the outer surface of theinsulating jacket 302 and in close proximity thereof. The presence of anasymmetric guided wave mode is shown by the high electromagnetic fieldstrengths at the top and bottom of the outer surface of the insulatingjacket 302 (in the orientation of the diagram)—as opposed to very smallfield strengths on the other sides of the insulating jacket 302.

The example shown corresponds to a 38 GHz electromagnetic wave guided bya wire with a diameter of 1.1 cm and a dielectric insulation ofthickness of 0.36 cm. Because the electromagnetic wave is guided by thetransmission medium 125 and the majority of the field strength isconcentrated in the air outside of the insulating jacket 302 within alimited distance of the outer surface, the guided wave can propagatelongitudinally down the transmission medium 125 with very low loss. Inthe example shown, this “limited distance” corresponds to a distancefrom the outer surface that is less than half the largest crosssectional dimension of the transmission medium 125. In this case, thelargest cross sectional dimension of the wire corresponds to the overalldiameter of 1.82 cm, however, this value can vary with the size andshape of the transmission medium 125. For example, should thetransmission medium 125 be of a rectangular shape with a height of 0.3cm and a width of 0.4 cm, the largest cross sectional dimension would bethe diagonal of 0.5 cm and the corresponding limited distance would be0.25 cm. The dimensions of the area containing the majority of the fieldstrength also vary with the frequency, and in general, increase ascarrier frequencies decrease.

It should also be noted that the components of a guided wavecommunication system, such as couplers and transmission media can havetheir own cut-off frequencies for each guided wave mode. The cut-offfrequency generally sets forth the lowest frequency that a particularguided wave mode is designed to be supported by that particularcomponent. In an example embodiment, the particular asymmetric mode ofpropagation shown is induced on the transmission medium 125 by anelectromagnetic wave having a frequency that falls within a limitedrange (such as Fc to 2Fc) of the lower cut-off frequency Fc for thisparticular asymmetric mode. The lower cut-off frequency Fc is particularto the characteristics of transmission medium 125. For embodiments asshown that include an inner conductor 301 surrounded by an insulatingjacket 302, this cutoff frequency can vary based on the dimensions andproperties of the insulating jacket 302 and potentially the dimensionsand properties of the inner conductor 301 and can be determinedexperimentally to have a desired mode pattern. It should be notedhowever, that similar effects can be found for a hollow dielectric orinsulator without an inner conductor. In this case, the cutoff frequencycan vary based on the dimensions and properties of the hollow dielectricor insulator.

At frequencies lower than the lower cut-off frequency, the asymmetricmode is difficult to induce in the transmission medium 125 and fails topropagate for all but trivial distances. As the frequency increasesabove the limited range of frequencies about the cut-off frequency, theasymmetric mode shifts more and more inward of the insulating jacket302. At frequencies much larger than the cut-off frequency, the fieldstrength is no longer concentrated outside of the insulating jacket, butprimarily inside of the insulating jacket 302. While the transmissionmedium 125 provides strong guidance to the electromagnetic wave andpropagation is still possible, ranges are more limited by increasedlosses due to propagation within the insulating jacket 302—as opposed tothe surrounding air.

Referring now to FIG. 4, a graphical diagram 400 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In particular, a cross section diagram 400,similar to FIG. 3 is shown with common reference numerals used to referto similar elements. The example shown corresponds to a 60 GHz waveguided by a wire with a diameter of 1.1 cm and a dielectric insulationof thickness of 0.36 cm. Because the frequency of the guided wave isabove the limited range of the cut-off frequency of this particularasymmetric mode, much of the field strength has shifted inward of theinsulating jacket 302. In particular, the field strength is concentratedprimarily inside of the insulating jacket 302. While the transmissionmedium 125 provides strong guidance to the electromagnetic wave andpropagation is still possible, ranges are more limited when comparedwith the embodiment of FIG. 3, by increased losses due to propagationwithin the insulating jacket 302.

Referring now to FIG. 5A, a graphical diagram illustrating an example,non-limiting embodiment of a frequency response is shown. In particular,diagram 500 presents a graph of end-to-end loss (in dB) as a function offrequency (in GHz), overlaid with electromagnetic field distributions510, 520 and 530 at three points for a 200 cm insulated medium voltagewire. The boundary between the insulator and the surrounding air isrepresented by reference numeral 525 in each electromagnetic fielddistribution.

As discussed in conjunction with FIG. 3, an example of a desiredasymmetric mode of propagation shown is induced on the transmissionmedium 125 by an electromagnetic wave having a frequency that fallswithin a limited range (such as Fc to 2Fc) of the lower cut-offfrequency Fc of the transmission medium for this particular asymmetricmode. In particular, the electromagnetic field distribution 520 at 6 GHzfalls within this modal “sweet spot” that enhances electromagnetic wavepropagation along an insulated transmission medium and reducesend-to-end transmission loss. In this particular mode, guided waves arepartially embedded in the insulator and partially radiating on the outersurface of the insulator. In this fashion, the electromagnetic waves are“lightly” coupled to the insulator so as to enable guidedelectromagnetic wave propagation at long distances with low propagationloss.

At lower frequencies represented by the electromagnetic fielddistribution 510 at 3 GHz, the asymmetric mode radiates more heavilygenerating higher propagation losses. At higher frequencies representedby the electromagnetic field distribution 530 at 9 GHz, the asymmetricmode shifts more and more inward of the insulating jacket providing toomuch absorption, again generating higher propagation losses.

Referring now to FIG. 5B, a graphical diagram 550 illustrating example,non-limiting embodiments of a longitudinal cross-section of atransmission medium 125, such as an insulated wire, depicting fields ofguided electromagnetic waves at various operating frequencies is shown.As shown in diagram 556, when the guided electromagnetic waves are atapproximately the cutoff frequency (f_(c)) corresponding to the modal“sweet spot”, the guided electromagnetic waves are loosely coupled tothe insulated wire so that absorption is reduced, and the fields of theguided electromagnetic waves are bound sufficiently to reduce the amountradiated into the environment (e.g., air). Because absorption andradiation of the fields of the guided electromagnetic waves is low,propagation losses are consequently low, enabling the guidedelectromagnetic waves to propagate for longer distances.

As shown in diagram 554, propagation losses increase when an operatingfrequency of the guide electromagnetic waves increases above abouttwo-times the cutoff frequency (f_(c))—or as referred to, above therange of the “sweet spot”. More of the field strength of theelectromagnetic wave is driven inside the insulating layer, increasingpropagation losses. At frequencies much higher than the cutoff frequency(f_(c)) the guided electromagnetic waves are strongly bound to theinsulated wire as a result of the fields emitted by the guidedelectromagnetic waves being concentrated in the insulation layer of thewire, as shown in diagram 552. This in turn raises propagation lossesfurther due to absorption of the guided electromagnetic waves by theinsulation layer. Similarly, propagation losses increase when theoperating frequency of the guided electromagnetic waves is substantiallybelow the cutoff frequency (f_(c)), as shown in diagram 558. Atfrequencies much lower than the cutoff frequency (f_(c)) the guidedelectromagnetic waves are weakly (or nominally) bound to the insulatedwire and thereby tend to radiate into the environment (e.g., air), whichin turn, raises propagation losses due to radiation of the guidedelectromagnetic waves.

Referring now to FIG. 6, a graphical diagram 600 illustrating anexample, non-limiting embodiment of an electromagnetic fielddistribution is shown. In this embodiment, a transmission medium 602 isa bare wire, as shown in cross section. The diagram 300 includesdifferent gray-scales that represent differing electromagnetic fieldstrengths generated by the propagation of a guided wave having asymmetrical and fundamental guided wave mode at a single carrierfrequency.

In this particular mode, electromagnetic waves are guided by thetransmission medium 602 to propagate along an outer surface of thetransmission medium—in this case, the outer surface of the bare wire.Electromagnetic waves are “lightly” coupled to the wire so as to enableelectromagnetic wave propagation at long distances with low propagationloss. As shown, the guided wave has a field structure that liessubstantially outside of the transmission medium 602 that serves toguide the electromagnetic waves. The regions inside the conductor 602have little or no field.

Referring now to FIG. 7, a block diagram 700 illustrating an example,non-limiting embodiment of an arc coupler is shown. In particular acoupling device is presented for use in a transmission device, such astransmission device 101 or 102 presented in conjunction with FIG. 1. Thecoupling device includes an arc coupler 704 coupled to a transmittercircuit 712 and termination or damper 714. The arc coupler 704 can bemade of a dielectric material, or other low-loss insulator (e.g.,TEFLON, polyethylene, etc.), or made of a conducting (e.g., metallic,non-metallic, etc.) material, or any combination of the foregoingmaterials. As shown, the arc coupler 704 operates as a waveguide and hasa wave 706 propagating as a guided wave about a waveguide surface of thearc coupler 704. In the embodiment shown, at least a portion of the arccoupler 704 can be placed near a wire 702 or other transmission medium,(such as transmission medium 125), in order to facilitate couplingbetween the arc coupler 704 and the wire 702 or other transmissionmedium, as described herein to launch the guided wave 708 on the wire.The arc coupler 704 can be placed such that a portion of the curved arccoupler 704 is tangential to, and parallel or substantially parallel tothe wire 702. The portion of the arc coupler 704 that is parallel to thewire can be an apex of the curve, or any point where a tangent of thecurve is parallel to the wire 702. When the arc coupler 704 ispositioned or placed thusly, the wave 706 travelling along the arccoupler 704 couples, at least in part, to the wire 702, and propagatesas guided wave 708 around or about the wire surface of the wire 702 andlongitudinally along the wire 702. The guided wave 708 can becharacterized as a surface wave or other electromagnetic wave that isguided by or bound to the wire 702 or other transmission medium.

A portion of the wave 706 that does not couple to the wire 702propagates as a wave 710 along the arc coupler 704. It will beappreciated that the arc coupler 704 can be configured and arranged in avariety of positions in relation to the wire 702 to achieve a desiredlevel of coupling or non-coupling of the wave 706 to the wire 702. Forexample, the curvature and/or length of the arc coupler 704 that isparallel or substantially parallel, as well as its separation distance(which can include zero separation distance in an embodiment), to thewire 702 can be varied without departing from example embodiments.Likewise, the arrangement of arc coupler 704 in relation to the wire 702may be varied based upon considerations of the respective intrinsiccharacteristics (e.g., thickness, composition, electromagneticproperties, etc.) of the wire 702 and the arc coupler 704, as well asthe characteristics (e.g., frequency, energy level, etc.) of the waves706 and 708.

The guided wave 708 stays parallel or substantially parallel to the wire702, even as the wire 702 bends and flexes. Bends in the wire 702 canincrease transmission losses, which are also dependent on wirediameters, frequency, and materials. If the dimensions of the arccoupler 704 are chosen for efficient power transfer, most of the powerin the wave 706 is transferred to the wire 702, with little powerremaining in wave 710. It will be appreciated that the guided wave 708can still be multi-modal in nature (discussed herein), including havingmodes that are non-fundamental or asymmetric, while traveling along apath that is parallel or substantially parallel to the wire 702, with orwithout a fundamental transmission mode. In an embodiment,non-fundamental or asymmetric modes can be utilized to minimizetransmission losses and/or obtain increased propagation distances.

It is noted that the term parallel is generally a geometric constructwhich often is not exactly achievable in real systems. Accordingly, theterm parallel as utilized in the subject disclosure represents anapproximation rather than an exact configuration when used to describeembodiments disclosed in the subject disclosure. In an embodiment,substantially parallel can include approximations that are within 30degrees of true parallel in all dimensions.

In an embodiment, the wave 706 can exhibit one or more wave propagationmodes. The arc coupler modes can be dependent on the shape and/or designof the coupler 704. The one or more arc coupler modes of wave 706 cangenerate, influence, or impact one or more wave propagation modes of theguided wave 708 propagating along wire 702. It should be particularlynoted however that the guided wave modes present in the guided wave 706may be the same or different from the guided wave modes of the guidedwave 708. In this fashion, one or more guided wave modes of the guidedwave 706 may not be transferred to the guided wave 708, and further oneor more guided wave modes of guided wave 708 may not have been presentin guided wave 706. It should also be noted that the cut-off frequencyof the arc coupler 704 for a particular guided wave mode may bedifferent than the cutoff frequency of the wire 702 or othertransmission medium for that same mode. For example, while the wire 702or other transmission medium may be operated slightly above its cutofffrequency for a particular guided wave mode, the arc coupler 704 may beoperated well above its cut-off frequency for that same mode for lowloss, slightly below its cut-off frequency for that same mode to, forexample, induce greater coupling and power transfer, or some other pointin relation to the arc coupler's cutoff frequency for that mode.

In an embodiment, the wave propagation modes on the wire 702 can besimilar to the arc coupler modes since both waves 706 and 708 propagateabout the outside of the arc coupler 704 and wire 702 respectively. Insome embodiments, as the wave 706 couples to the wire 702, the modes canchange form, or new modes can be created or generated, due to thecoupling between the arc coupler 704 and the wire 702. For example,differences in size, material, and/or impedances of the arc coupler 704and wire 702 may create additional modes not present in the arc couplermodes and/or suppress some of the arc coupler modes. The wavepropagation modes can comprise the fundamental transverseelectromagnetic mode (Quasi-TEM₀₀), where only small electric and/ormagnetic fields extend in the direction of propagation, and the electricand magnetic fields extend radially outwards while the guided wavepropagates along the wire. This guided wave mode can be donut shaped,where few of the electromagnetic fields exist within the arc coupler 704or wire 702.

Waves 706 and 708 can comprise a fundamental TEM mode where the fieldsextend radially outwards, and also comprise other, non-fundamental(e.g., asymmetric, higher-level, etc.) modes. While particular wavepropagation modes are discussed above, other wave propagation modes arelikewise possible such as transverse electric (TE) and transversemagnetic (TM) modes, based on the frequencies employed, the design ofthe arc coupler 704, the dimensions and composition of the wire 702, aswell as its surface characteristics, its insulation if present, theelectromagnetic properties of the surrounding environment, etc. Itshould be noted that, depending on the frequency, the electrical andphysical characteristics of the wire 702 and the particular wavepropagation modes that are generated, guided wave 708 can travel alongthe conductive surface of an oxidized uninsulated wire, an unoxidizeduninsulated wire, an insulated wire and/or along the insulating surfaceof an insulated wire.

In an embodiment, a diameter of the arc coupler 704 is smaller than thediameter of the wire 702. For the millimeter-band wavelength being used,the arc coupler 704 supports a single waveguide mode that makes up wave706. This single waveguide mode can change as it couples to the wire 702as guided wave 708. If the arc coupler 704 were larger, more than onewaveguide mode can be supported, but these additional waveguide modesmay not couple to the wire 702 as efficiently, and higher couplinglosses can result. However, in some alternative embodiments, thediameter of the arc coupler 704 can be equal to or larger than thediameter of the wire 702, for example, where higher coupling losses aredesirable or when used in conjunction with other techniques to otherwisereduce coupling losses (e.g., impedance matching with tapering, etc.).

In an embodiment, the wavelength of the waves 706 and 708 are comparablein size, or smaller than a circumference of the arc coupler 704 and thewire 702. In an example, if the wire 702 has a diameter of 0.5 cm, and acorresponding circumference of around 1.5 cm, the wavelength of thetransmission is around 1.5 cm or less, corresponding to a frequency of70 GHz or greater. In another embodiment, a suitable frequency of thetransmission and the carrier-wave signal is in the range of 30-100 GHz,perhaps around 30-60 GHz, and around 38 GHz in one example. In anembodiment, when the circumference of the arc coupler 704 and wire 702is comparable in size to, or greater, than a wavelength of thetransmission, the waves 706 and 708 can exhibit multiple wavepropagation modes including fundamental and/or non-fundamental(symmetric and/or asymmetric) modes that propagate over sufficientdistances to support various communication systems described herein. Thewaves 706 and 708 can therefore comprise more than one type of electricand magnetic field configuration. In an embodiment, as the guided wave708 propagates down the wire 702, the electrical and magnetic fieldconfigurations will remain the same from end to end of the wire 702. Inother embodiments, as the guided wave 708 encounters interference(distortion or obstructions) or loses energy due to transmission lossesor scattering, the electric and magnetic field configurations can changeas the guided wave 708 propagates down wire 702.

In an embodiment, the arc coupler 704 can be composed of nylon, TEFLON,polyethylene, a polyamide, or other plastics. In other embodiments,other dielectric materials are possible. The wire surface of wire 702can be metallic with either a bare metallic surface, or can be insulatedusing plastic, dielectric, insulator or other coating, jacket orsheathing. In an embodiment, a dielectric or otherwisenon-conducting/insulated waveguide can be paired with either abare/metallic wire or insulated wire. In other embodiments, a metallicand/or conductive waveguide can be paired with a bare/metallic wire orinsulated wire. In an embodiment, an oxidation layer on the baremetallic surface of the wire 702 (e.g., resulting from exposure of thebare metallic surface to oxygen/air) can also provide insulating ordielectric properties similar to those provided by some insulators orsheathings.

It is noted that the graphical representations of waves 706, 708 and 710are presented merely to illustrate the principles that wave 706 inducesor otherwise launches a guided wave 708 on a wire 702 that operates, forexample, as a single wire transmission line. Wave 710 represents theportion of wave 706 that remains on the arc coupler 704 after thegeneration of guided wave 708. The actual electric and magnetic fieldsgenerated as a result of such wave propagation may vary depending on thefrequencies employed, the particular wave propagation mode or modes, thedesign of the arc coupler 704, the dimensions and composition of thewire 702, as well as its surface characteristics, its optionalinsulation, the electromagnetic properties of the surroundingenvironment, etc.

It is noted that arc coupler 704 can include a termination circuit ordamper 714 at the end of the arc coupler 704 that can absorb leftoverradiation or energy from wave 710. The termination circuit or damper 714can prevent and/or minimize the leftover radiation or energy from wave710 reflecting back toward transmitter circuit 712. In an embodiment,the termination circuit or damper 714 can include termination resistors,and/or other components that perform impedance matching to attenuatereflection. In some embodiments, if the coupling efficiencies are highenough, and/or wave 710 is sufficiently small, it may not be necessaryto use a termination circuit or damper 714. For the sake of simplicity,these transmitter 712 and termination circuits or dampers 714 may not bedepicted in the other figures, but in those embodiments, transmitter andtermination circuits or dampers may possibly be used.

Further, while a single arc coupler 704 is presented that generates asingle guided wave 708, multiple arc couplers 704 placed at differentpoints along the wire 702 and/or at different azimuthal orientationsabout the wire can be employed to generate and receive multiple guidedwaves 708 at the same or different frequencies, at the same or differentphases, at the same or different wave propagation modes.

FIG. 8, a block diagram 800 illustrating an example, non-limitingembodiment of an arc coupler is shown. In the embodiment shown, at leasta portion of the coupler 704 can be placed near a wire 702 or othertransmission medium, (such as transmission medium 125), in order tofacilitate coupling between the arc coupler 704 and the wire 702 orother transmission medium, to extract a portion of the guided wave 806as a guided wave 808 as described herein. The arc coupler 704 can beplaced such that a portion of the curved arc coupler 704 is tangentialto, and parallel or substantially parallel to the wire 702. The portionof the arc coupler 704 that is parallel to the wire can be an apex ofthe curve, or any point where a tangent of the curve is parallel to thewire 702. When the arc coupler 704 is positioned or placed thusly, thewave 806 travelling along the wire 702 couples, at least in part, to thearc coupler 704, and propagates as guided wave 808 along the arc coupler704 to a receiving device (not expressly shown). A portion of the wave806 that does not couple to the arc coupler propagates as wave 810 alongthe wire 702 or other transmission medium.

In an embodiment, the wave 806 can exhibit one or more wave propagationmodes. The arc coupler modes can be dependent on the shape and/or designof the coupler 704. The one or more modes of guided wave 806 cangenerate, influence, or impact one or more guide-wave modes of theguided wave 808 propagating along the arc coupler 704. It should beparticularly noted however that the guided wave modes present in theguided wave 806 may be the same or different from the guided wave modesof the guided wave 808. In this fashion, one or more guided wave modesof the guided wave 806 may not be transferred to the guided wave 808,and further one or more guided wave modes of guided wave 808 may nothave been present in guided wave 806.

Referring now to FIG. 9A, a block diagram 900 illustrating an example,non-limiting embodiment of a stub coupler is shown. In particular acoupling device that includes stub coupler 904 is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. The stub coupler 904 can be made of adielectric material, or other low-loss insulator (e.g., TEFLON,polyethylene and etc.), or made of a conducting (e.g., metallic,non-metallic, etc.) material, or any combination of the foregoingmaterials. As shown, the stub coupler 904 operates as a waveguide andhas a wave 906 propagating as a guided wave about a waveguide surface ofthe stub coupler 904. In the embodiment shown, at least a portion of thestub coupler 904 can be placed near a wire 702 or other transmissionmedium, (such as transmission medium 125), in order to facilitatecoupling between the stub coupler 904 and the wire 702 or othertransmission medium, as described herein to launch the guided wave 908on the wire.

In an embodiment, the stub coupler 904 is curved, and an end of the stubcoupler 904 can be tied, fastened, or otherwise mechanically coupled toa wire 702. When the end of the stub coupler 904 is fastened to the wire702, the end of the stub coupler 904 is parallel or substantiallyparallel to the wire 702. Alternatively, another portion of thedielectric waveguide beyond an end can be fastened or coupled to wire702 such that the fastened or coupled portion is parallel orsubstantially parallel to the wire 702. The fastener 910 can be a nyloncable tie or other type of non-conducting/dielectric material that iseither separate from the stub coupler 904 or constructed as anintegrated component of the stub coupler 904. The stub coupler 904 canbe adjacent to the wire 702 without surrounding the wire 702.

Like the arc coupler 704 described in conjunction with FIG. 7, when thestub coupler 904 is placed with the end parallel to the wire 702, theguided wave 906 travelling along the stub coupler 904 couples to thewire 702, and propagates as guided wave 908 about the wire surface ofthe wire 702. In an example embodiment, the guided wave 908 can becharacterized as a surface wave or other electromagnetic wave.

It is noted that the graphical representations of waves 906 and 908 arepresented merely to illustrate the principles that wave 906 induces orotherwise launches a guided wave 908 on a wire 702 that operates, forexample, as a single wire transmission line. The actual electric andmagnetic fields generated as a result of such wave propagation may varydepending on one or more of the shape and/or design of the coupler, therelative position of the dielectric waveguide to the wire, thefrequencies employed, the design of the stub coupler 904, the dimensionsand composition of the wire 702, as well as its surface characteristics,its optional insulation, the electromagnetic properties of thesurrounding environment, etc.

In an embodiment, an end of stub coupler 904 can taper towards the wire702 in order to increase coupling efficiencies. Indeed, the tapering ofthe end of the stub coupler 904 can provide impedance matching to thewire 702 and reduce reflections, according to an example embodiment ofthe subject disclosure. For example, an end of the stub coupler 904 canbe gradually tapered in order to obtain a desired level of couplingbetween waves 906 and 908 as illustrated in FIG. 9A.

In an embodiment, the fastener 910 can be placed such that there is ashort length of the stub coupler 904 between the fastener 910 and an endof the stub coupler 904. Maximum coupling efficiencies are realized inthis embodiment when the length of the end of the stub coupler 904 thatis beyond the fastener 910 is at least several wavelengths long forwhatever frequency is being transmitted.

Turning now to FIG. 9B, a diagram 950 illustrating an example,non-limiting embodiment of an electromagnetic distribution in accordancewith various aspects described herein is shown. In particular, anelectromagnetic distribution is presented in two dimensions for atransmission device that includes coupler 952, shown in an example stubcoupler constructed of a dielectric material. The coupler 952 couples anelectromagnetic wave for propagation as a guided wave along an outersurface of a wire 702 or other transmission medium.

The coupler 952 guides the electromagnetic wave to a junction at x₀ viaa symmetrical guided wave mode. While some of the energy of theelectromagnetic wave that propagates along the coupler 952 is outside ofthe coupler 952, the majority of the energy of this electromagnetic waveis contained within the coupler 952. The junction at x₀ couples theelectromagnetic wave to the wire 702 or other transmission medium at anazimuthal angle corresponding to the bottom of the transmission medium.This coupling induces an electromagnetic wave that is guided topropagate along the outer surface of the wire 702 or other transmissionmedium via at least one guided wave mode in direction 956. The majorityof the energy of the guided electromagnetic wave is outside or, but inclose proximity to the outer surface of the wire 702 or othertransmission medium. In the example shown, the junction at x₀ forms anelectromagnetic wave that propagates via both a symmetrical mode and atleast one asymmetrical surface mode, such as the first order modepresented in conjunction with FIG. 3, that skims the surface of the wire702 or other transmission medium.

It is noted that the graphical representations of guided waves arepresented merely to illustrate an example of guided wave coupling andpropagation. The actual electric and magnetic fields generated as aresult of such wave propagation may vary depending on the frequenciesemployed, the design and/or configuration of the coupler 952, thedimensions and composition of the wire 702 or other transmission medium,as well as its surface characteristics, its insulation if present, theelectromagnetic properties of the surrounding environment, etc.

Turning now to FIG. 10A, illustrated is a block diagram 1000 of anexample, non-limiting embodiment of a coupler and transceiver system inaccordance with various aspects described herein. The system is anexample of transmission device 101 or 102. In particular, thecommunication interface 1008 is an example of communications interface205, the stub coupler 1002 is an example of coupler 220, and thetransmitter/receiver device 1006, diplexer 1016, power amplifier 1014,low noise amplifier 1018, frequency mixers 1010 and 1020 and localoscillator 1012 collectively form an example of transceiver 210.

In operation, the transmitter/receiver device 1006 launches and receiveswaves (e.g., guided wave 1004 onto stub coupler 1002). The guided waves1004 can be used to transport signals received from and sent to a hostdevice, base station, mobile devices, a building or other device by wayof a communications interface 1008. The communications interface 1008can be an integral part of system 1000. Alternatively, thecommunications interface 1008 can be tethered to system 1000. Thecommunications interface 1008 can comprise a wireless interface forinterfacing to the host device, base station, mobile devices, a buildingor other device utilizing any of various wireless signaling protocols(e.g., LTE, WiFi, WiMAX, IEEE 802 series, etc.) including an infraredprotocol such as an infrared data association (IrDA) protocol or otherline of sight optical protocol. The communications interface 1008 canalso comprise a wired interface such as a fiber optic line, coaxialcable, twisted pair, category 5 (CAT-5) cable or other suitable wired oroptical mediums for communicating with the host device, base station,mobile devices, a building or other device via a protocol such as anEthernet protocol, universal serial bus (USB) protocol, a data overcable service interface specification (DOCSIS) protocol, a digitalsubscriber line (DSL) protocol, a Firewire (IEEE 1394) protocol, orother wired or optical protocol. For embodiments where system 1000functions as a repeater, the communications interface 1008 may not benecessary.

The output signals (e.g., Tx) of the communications interface 1008 canbe combined with a carrier wave (e.g., millimeter-wave carrier wave)generated by a local oscillator 1012 at frequency mixer 1010. Frequencymixer 1010 can use heterodyning techniques or other frequency shiftingtechniques to frequency shift the output signals from communicationsinterface 1008. For example, signals sent to and from the communicationsinterface 1008 can be modulated signals such as orthogonal frequencydivision multiplexed (OFDM) signals formatted in accordance with aLong-Term Evolution (LTE) wireless protocol or other wireless 3G, 4G, 5Gor higher voice and data protocol, a ZIGBEE®, WIMAX, UltraWideband orIEEE 802.11 wireless protocol; a wired protocol such as an Ethernetprotocol, universal serial bus (USB) protocol, a data over cable serviceinterface specification (DOCSIS) protocol, a digital subscriber line(DSL) protocol, a Firewire (IEEE 1394) protocol or other wired orwireless protocol. In an example embodiment, this frequency conversioncan be done in the analog domain, and as a result, the frequencyshifting can be done without regard to the type of communicationsprotocol used by a base station, mobile devices, or in-building devices.As new communications technologies are developed, the communicationsinterface 1008 can be upgraded (e.g., updated with software, firmware,and/or hardware) or replaced and the frequency shifting and transmissionapparatus can remain, simplifying upgrades. The carrier wave can then besent to a power amplifier (“PA”) 1014 and can be transmitted via thetransmitter receiver device 1006 via the diplexer 1016.

Signals received from the transmitter/receiver device 1006 that aredirected towards the communications interface 1008 can be separated fromother signals via diplexer 1016. The received signal can then be sent tolow noise amplifier (“LNA”) 1018 for amplification. A frequency mixer1020, with help from local oscillator 1012 can downshift the receivedsignal (which is in the millimeter-wave band or around 38 GHz in someembodiments) to the native frequency. The communications interface 1008can then receive the transmission at an input port (Rx).

In an embodiment, transmitter/receiver device 1006 can include acylindrical or non-cylindrical metal (which, for example, can be hollowin an embodiment, but not necessarily drawn to scale) or otherconducting or non-conducting waveguide and an end of the stub coupler1002 can be placed in or in proximity to the waveguide or thetransmitter/receiver device 1006 such that when the transmitter/receiverdevice 1006 generates a transmission, the guided wave couples to stubcoupler 1002 and propagates as a guided wave 1004 about the waveguidesurface of the stub coupler 1002. In some embodiments, the guided wave1004 can propagate in part on the outer surface of the stub coupler 1002and in part inside the stub coupler 1002. In other embodiments, theguided wave 1004 can propagate substantially or completely on the outersurface of the stub coupler 1002. In yet other embodiments, the guidedwave 1004 can propagate substantially or completely inside the stubcoupler 1002. In this latter embodiment, the guided wave 1004 canradiate at an end of the stub coupler 1002 (such as the tapered endshown in FIG. 4) for coupling to a transmission medium such as a wire702 of FIG. 7. Similarly, if guided wave 1004 is incoming (coupled tothe stub coupler 1002 from a wire 702), guided wave 1004 then enters thetransmitter/receiver device 1006 and couples to the cylindricalwaveguide or conducting waveguide. While transmitter/receiver device1006 is shown to include a separate waveguide—an antenna, cavityresonator, klystron, magnetron, travelling wave tube, or other radiatingelement can be employed to induce a guided wave on the coupler 1002,with or without the separate waveguide.

In an embodiment, stub coupler 1002 can be wholly constructed of adielectric material (or another suitable insulating material), withoutany metallic or otherwise conducting materials therein. Stub coupler1002 can be composed of nylon, TEFLON, polyethylene, a polyamide, otherplastics, or other materials that are non-conducting and suitable forfacilitating transmission of electromagnetic waves at least in part onan outer surface of such materials. In another embodiment, stub coupler1002 can include a core that is conducting/metallic, and have anexterior dielectric surface. Similarly, a transmission medium thatcouples to the stub coupler 1002 for propagating electromagnetic wavesinduced by the stub coupler 1002 or for supplying electromagnetic wavesto the stub coupler 1002 can, in addition to being a bare or insulatedwire, be wholly constructed of a dielectric material (or anothersuitable insulating material), without any metallic or otherwiseconducting materials therein.

It is noted that although FIG. 10A shows that the opening of transmitterreceiver device 1006 is much wider than the stub coupler 1002, this isnot to scale, and that in other embodiments the width of the stubcoupler 1002 is comparable or slightly smaller than the opening of thehollow waveguide. It is also not shown, but in an embodiment, an end ofthe coupler 1002 that is inserted into the transmitter/receiver device1006 tapers down in order to reduce reflection and increase couplingefficiencies.

Before coupling to the stub coupler 1002, the one or more waveguidemodes of the guided wave generated by the transmitter/receiver device1006 can couple to the stub coupler 1002 to induce one or more wavepropagation modes of the guided wave 1004. The wave propagation modes ofthe guided wave 1004 can be different than the hollow metal waveguidemodes due to the different characteristics of the hollow metal waveguideand the dielectric waveguide. For instance, wave propagation modes ofthe guided wave 1004 can comprise the fundamental transverseelectromagnetic mode (Quasi-TEM₀₀), where only small electrical and/ormagnetic fields extend in the direction of propagation, and the electricand magnetic fields extend radially outwards from the stub coupler 1002while the guided waves propagate along the stub coupler 1002. Thefundamental transverse electromagnetic mode wave propagation mode may ormay not exist inside a waveguide that is hollow. Therefore, the hollowmetal waveguide modes that are used by transmitter/receiver device 1006are waveguide modes that can couple effectively and efficiently to wavepropagation modes of stub coupler 1002.

It will be appreciated that other constructs or combinations of thetransmitter/receiver device 1006 and stub coupler 1002 are possible. Forexample, a stub coupler 1002′ can be placed tangentially or in parallel(with or without a gap) with respect to an outer surface of the hollowmetal waveguide of the transmitter/receiver device 1006′ (correspondingcircuitry not shown) as depicted by reference 1000′ of FIG. 10B. Inanother embodiment, not shown by reference 1000′, the stub coupler 1002′can be placed inside the hollow metal waveguide of thetransmitter/receiver device 1006′ without an axis of the stub coupler1002′ being coaxially aligned with an axis of the hollow metal waveguideof the transmitter/receiver device 1006′. In either of theseembodiments, the guided wave generated by the transmitter/receiverdevice 1006′ can couple to a surface of the stub coupler 1002′ to induceone or more wave propagation modes of the guided wave 1004′ on the stubcoupler 1002′ including a fundamental mode (e.g., a symmetric mode)and/or a non-fundamental mode (e.g., asymmetric mode).

In one embodiment, the guided wave 1004′ can propagate in part on theouter surface of the stub coupler 1002′ and in part inside the stubcoupler 1002′. In another embodiment, the guided wave 1004′ canpropagate substantially or completely on the outer surface of the stubcoupler 1002′. In yet other embodiments, the guided wave 1004′ canpropagate substantially or completely inside the stub coupler 1002′. Inthis latter embodiment, the guided wave 1004′ can radiate at an end ofthe stub coupler 1002′ (such as the tapered end shown in FIG. 9) forcoupling to a transmission medium such as a wire 702 of FIG. 9.

It will be further appreciated that other constructs thetransmitter/receiver device 1006 are possible. For example, a hollowmetal waveguide of a transmitter/receiver device 1006″ (correspondingcircuitry not shown), depicted in FIG. 10B as reference 1000″, can beplaced tangentially or in parallel (with or without a gap) with respectto an outer surface of a transmission medium such as the wire 702 ofFIG. 4 without the use of the stub coupler 1002. In this embodiment, theguided wave generated by the transmitter/receiver device 1006″ cancouple to a surface of the wire 702 to induce one or more wavepropagation modes of a guided wave 908 on the wire 702 including afundamental mode (e.g., a symmetric mode) and/or a non-fundamental mode(e.g., asymmetric mode). In another embodiment, the wire 702 can bepositioned inside a hollow metal waveguide of a transmitter/receiverdevice 1006′″ (corresponding circuitry not shown) so that an axis of thewire 702 is coaxially (or not coaxially) aligned with an axis of thehollow metal waveguide without the use of the stub coupler 1002—see FIG.10B reference 1000′″. In this embodiment, the guided wave generated bythe transmitter/receiver device 1006′″ can couple to a surface of thewire 702 to induce one or more wave propagation modes of a guided wave908 on the wire including a fundamental mode (e.g., a symmetric mode)and/or a non-fundamental mode (e.g., asymmetric mode).

In the embodiments of 1000″ and 1000′″, for a wire 702 having aninsulated outer surface, the guided wave 908 can propagate in part onthe outer surface of the insulator and in part inside the insulator. Inembodiments, the guided wave 908 can propagate substantially orcompletely on the outer surface of the insulator, or substantially orcompletely inside the insulator. In the embodiments of 1000″ and 1000′″,for a wire 702 that is a bare conductor, the guided wave 908 canpropagate in part on the outer surface of the conductor and in partinside the conductor. In another embodiment, the guided wave 908 canpropagate substantially or completely on the outer surface of theconductor.

Referring now to FIG. 11, a block diagram 1100 illustrating an example,non-limiting embodiment of a dual stub coupler is shown. In particular,a dual coupler design is presented for use in a transmission device,such as transmission device 101 or 102 presented in conjunction withFIG. 1. In an embodiment, two or more couplers (such as the stubcouplers 1104 and 1106) can be positioned around a wire 1102 in order toreceive guided wave 1108. In an embodiment, one coupler is enough toreceive the guided wave 1108. In that case, guided wave 1108 couples tocoupler 1104 and propagates as guided wave 1110. If the field structureof the guided wave 1108 oscillates or undulates around the wire 1102 dueto the particular guided wave mode(s) or various outside factors, thencoupler 1106 can be placed such that guided wave 1108 couples to coupler1106. In some embodiments, four or more couplers can be placed around aportion of the wire 1102, e.g., at 90 degrees or another spacing withrespect to each other, in order to receive guided waves that mayoscillate or rotate around the wire 1102, that have been induced atdifferent azimuthal orientations or that have non-fundamental or higherorder modes that, for example, have lobes and/or nulls or otherasymmetries that are orientation dependent. However, it will beappreciated that there may be less than or more than four couplersplaced around a portion of the wire 1102 without departing from exampleembodiments.

It should be noted that while couplers 1106 and 1104 are illustrated asstub couplers, any other of the coupler designs described hereinincluding arc couplers, antenna or horn couplers, magnetic couplers,etc., could likewise be used. It will also be appreciated that whilesome example embodiments have presented a plurality of couplers aroundat least a portion of a wire 1102, this plurality of couplers can alsobe considered as part of a single coupler system having multiple couplersubcomponents. For example, two or more couplers can be manufactured assingle system that can be installed around a wire in a singleinstallation such that the couplers are either pre-positioned oradjustable relative to each other (either manually or automatically witha controllable mechanism such as a motor or other actuator) inaccordance with the single system.

Receivers coupled to couplers 1106 and 1104 can use diversity combiningto combine signals received from both couplers 1106 and 1104 in order tomaximize the signal quality. In other embodiments, if one or the otherof the couplers 1104 and 1106 receive a transmission that is above apredetermined threshold, receivers can use selection diversity whendeciding which signal to use. Further, while reception by a plurality ofcouplers 1106 and 1104 is illustrated, transmission by couplers 1106 and1104 in the same configuration can likewise take place. In particular, awide range of multi-input multi-output (MIMO) transmission and receptiontechniques can be employed for transmissions where a transmissiondevice, such as transmission device 101 or 102 presented in conjunctionwith FIG. 1 includes multiple transceivers and multiple couplers.

It is noted that the graphical representations of waves 1108 and 1110are presented merely to illustrate the principles that guided wave 1108induces or otherwise launches a wave 1110 on a coupler 1104. The actualelectric and magnetic fields generated as a result of such wavepropagation may vary depending on the frequencies employed, the designof the coupler 1104, the dimensions and composition of the wire 1102, aswell as its surface characteristics, its insulation if any, theelectromagnetic properties of the surrounding environment, etc.

Referring now to FIG. 12, a block diagram 1200 illustrating an example,non-limiting embodiment of a repeater system is shown. In particular, arepeater device 1210 is presented for use in a transmission device, suchas transmission device 101 or 102 presented in conjunction with FIG. 1.In this system, two couplers 1204 and 1214 can be placed near a wire1202 or other transmission medium such that guided waves 1205propagating along the wire 1202 are extracted by coupler 1204 as wave1206 (e.g. as a guided wave), and then are boosted or repeated byrepeater device 1210 and launched as a wave 1216 (e.g. as a guided wave)onto coupler 1214. The wave 1216 can then be launched on the wire 1202and continue to propagate along the wire 1202 as a guided wave 1217. Inan embodiment, the repeater device 1210 can receive at least a portionof the power utilized for boosting or repeating through magneticcoupling with the wire 1202, for example, when the wire 1202 is a powerline or otherwise contains a power-carrying conductor. It should benoted that while couplers 1204 and 1214 are illustrated as stubcouplers, any other of the coupler designs described herein includingarc couplers, antenna or horn couplers, magnetic couplers, or the like,could likewise be used.

In some embodiments, repeater device 1210 can repeat the transmissionassociated with wave 1206, and in other embodiments, repeater device1210 can include a communications interface 205 that extracts data orother signals from the wave 1206 for supplying such data or signals toanother network and/or one or more other devices as communicationsignals 110 or 112 and/or receiving communication signals 110 or 112from another network and/or one or more other devices and launch guidedwave 1216 having embedded therein the received communication signals 110or 112. In a repeater configuration, receiver waveguide 1208 can receivethe wave 1206 from the coupler 1204 and transmitter waveguide 1212 canlaunch guided wave 1216 onto coupler 1214 as guided wave 1217. Betweenreceiver waveguide 1208 and transmitter waveguide 1212, the signalembedded in guided wave 1206 and/or the guided wave 1216 itself can beamplified to correct for signal loss and other inefficiencies associatedwith guided wave communications or the signal can be received andprocessed to extract the data contained therein and regenerated fortransmission. In an embodiment, the receiver waveguide 1208 can beconfigured to extract data from the signal, process the data to correctfor data errors utilizing for example error correcting codes, andregenerate an updated signal with the corrected data. The transmitterwaveguide 1212 can then transmit guided wave 1216 with the updatedsignal embedded therein. In an embodiment, a signal embedded in guidedwave 1206 can be extracted from the transmission and processed forcommunication with another network and/or one or more other devices viacommunications interface 205 as communication signals 110 or 112.Similarly, communication signals 110 or 112 received by thecommunications interface 205 can be inserted into a transmission ofguided wave 1216 that is generated and launched onto coupler 1214 bytransmitter waveguide 1212.

It is noted that although FIG. 12 shows guided wave transmissions 1206and 1216 entering from the left and exiting to the right respectively,this is merely a simplification and is not intended to be limiting. Inother embodiments, receiver waveguide 1208 and transmitter waveguide1212 can also function as transmitters and receivers respectively,allowing the repeater device 1210 to be bi-directional.

In an embodiment, repeater device 1210 can be placed at locations wherethere are discontinuities or obstacles on the wire 1202 or othertransmission medium. In the case where the wire 1202 is a power line,these obstacles can include transformers, connections, utility poles,and other such power line devices. The repeater device 1210 can help theguided (e.g., surface) waves jump over these obstacles on the line andboost the transmission power at the same time. In other embodiments, acoupler can be used to jump over the obstacle without the use of arepeater device. In that embodiment, both ends of the coupler can betied or fastened to the wire, thus providing a path for the guided waveto travel without being blocked by the obstacle.

Turning now to FIG. 13, illustrated is a block diagram 1300 of anexample, non-limiting embodiment of a bidirectional repeater inaccordance with various aspects described herein. In particular, abidirectional repeater device 1306 is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. It should be noted that while the couplers areillustrated as stub couplers, any other of the coupler designs describedherein including arc couplers, antenna or horn couplers, magneticcouplers, or the like, could likewise be used. The bidirectionalrepeater 1306 can employ diversity paths in the case of when two or morewires or other transmission media are present. Since guided wavetransmissions have different transmission efficiencies and couplingefficiencies for transmission medium of different types such asinsulated wires, un-insulated wires or other types of transmission mediaand further, if exposed to the elements, can be affected by weather, andother atmospheric conditions, it can be advantageous to selectivelytransmit on different transmission media at certain times. In variousembodiments, the various transmission media can be designated as aprimary, secondary, tertiary, etc. whether or not such designationindicates a preference of one transmission medium over another.

In the embodiment shown, the transmission media include an insulated oruninsulated wire 1302 and an insulated or uninsulated wire 1304(referred to herein as wires 1302 and 1304, respectively). The repeaterdevice 1306 uses a receiver coupler 1308 to receive a guided wavetraveling along wire 1302 and repeats the transmission using transmitterwaveguide 1310 as a guided wave along wire 1304. In other embodiments,repeater device 1306 can switch from the wire 1304 to the wire 1302, orcan repeat the transmissions along the same paths. Repeater device 1306can include sensors, or be in communication with sensors (or a networkmanagement system 1601 depicted in FIG. 16A) that indicate conditionsthat can affect the transmission. Based on the feedback received fromthe sensors, the repeater device 1306 can make the determination aboutwhether to keep the transmission along the same wire, or transfer thetransmission to the other wire.

Turning now to FIG. 14, illustrated is a block diagram 1400 illustratingan example, non-limiting embodiment of a bidirectional repeater system.In particular, a bidirectional repeater system is presented for use in atransmission device, such as transmission device 101 or 102 presented inconjunction with FIG. 1. The bidirectional repeater system includeswaveguide coupling devices 1402 and 1404 that receive and transmittransmissions from other coupling devices located in a distributedantenna system or backhaul system.

In various embodiments, waveguide coupling device 1402 can receive atransmission from another waveguide coupling device, wherein thetransmission has a plurality of subcarriers. Diplexer 1406 can separatethe transmission from other transmissions, and direct the transmissionto low-noise amplifier (“LNA”) 1408. A frequency mixer 1428, with helpfrom a local oscillator 1412, can downshift the transmission (which isin the millimeter-wave band or around 38 GHz in some embodiments) to alower frequency, such as a cellular band (˜1.9 GHz) for a distributedantenna system, a native frequency, or other frequency for a backhaulsystem. An extractor (or demultiplexer) 1432 can extract the signal on asubcarrier and direct the signal to an output component 1422 foroptional amplification, buffering or isolation by power amplifier 1424for coupling to communications interface 205. The communicationsinterface 205 can further process the signals received from the poweramplifier 1424 or otherwise transmit such signals over a wireless orwired interface to other devices such as a base station, mobile devices,a building, etc. For the signals that are not being extracted at thislocation, extractor 1432 can redirect them to another frequency mixer1436, where the signals are used to modulate a carrier wave generated bylocal oscillator 1414. The carrier wave, with its subcarriers, isdirected to a power amplifier (“PA”) 1416 and is retransmitted bywaveguide coupling device 1404 to another system, via diplexer 1420.

An LNA 1426 can be used to amplify, buffer or isolate signals that arereceived by the communication interface 205 and then send the signal toa multiplexer 1434 which merges the signal with signals that have beenreceived from waveguide coupling device 1404. The signals received fromcoupling device 1404 have been split by diplexer 1420, and then passedthrough LNA 1418, and downshifted in frequency by frequency mixer 1438.When the signals are combined by multiplexer 1434, they are upshifted infrequency by frequency mixer 1430, and then boosted by PA 1410, andtransmitted to another system by waveguide coupling device 1402. In anembodiment bidirectional repeater system can be merely a repeaterwithout the output device 1422. In this embodiment, the multiplexer 1434would not be utilized and signals from LNA 1418 would be directed tomixer 1430 as previously described. It will be appreciated that in someembodiments, the bidirectional repeater system could also be implementedusing two distinct and separate unidirectional repeaters. In analternative embodiment, a bidirectional repeater system could also be abooster or otherwise perform retransmissions without downshifting andupshifting. Indeed in example embodiment, the retransmissions can bebased upon receiving a signal or guided wave and performing some signalor guided wave processing or reshaping, filtering, and/or amplification,prior to retransmission of the signal or guided wave.

Referring now to FIG. 15, a block diagram 1500 illustrating an example,non-limiting embodiment of a guided wave communications system is shown.This diagram depicts an exemplary environment in which a guided wavecommunication system, such as the guided wave communication systempresented in conjunction with FIG. 1, can be used.

To provide network connectivity to additional base station devices, abackhaul network that links the communication cells (e.g., microcellsand macrocells) to network devices of a core network correspondinglyexpands. Similarly, to provide network connectivity to a distributedantenna system, an extended communication system that links base stationdevices and their distributed antennas is desirable. A guided wavecommunication system 1500 such as shown in FIG. 15 can be provided toenable alternative, increased or additional network connectivity and awaveguide coupling system can be provided to transmit and/or receiveguided wave (e.g., surface wave) communications on a transmission mediumsuch as a wire that operates as a single-wire transmission line (e.g., autility line), and that can be used as a waveguide and/or that otherwiseoperates to guide the transmission of an electromagnetic wave.

The guided wave communication system 1500 can comprise a first instanceof a distribution system 1550 that includes one or more base stationdevices (e.g., base station device 1504) that are communicably coupledto a central office 1501 and/or a macrocell site 1502. Base stationdevice 1504 can be connected by a wired (e.g., fiber and/or cable), orby a wireless (e.g., microwave wireless) connection to the macrocellsite 1502 and the central office 1501. A second instance of thedistribution system 1560 can be used to provide wireless voice and dataservices to mobile device 1522 and to residential and/or commercialestablishments 1542 (herein referred to as establishments 1542). System1500 can have additional instances of the distribution systems 1550 and1560 for providing voice and/or data services to mobile devices1522-1524 and establishments 1542 as shown in FIG. 15.

Macrocells such as macrocell site 1502 can have dedicated connections toa mobile network and base station device 1504 or can share and/orotherwise use another connection. Central office 1501 can be used todistribute media content and/or provide internet service provider (ISP)services to mobile devices 1522-1524 and establishments 1542. Thecentral office 1501 can receive media content from a constellation ofsatellites 1530 (one of which is shown in FIG. 15) or other sources ofcontent, and distribute such content to mobile devices 1522-1524 andestablishments 1542 via the first and second instances of thedistribution system 1550 and 1560. The central office 1501 can also becommunicatively coupled to the Internet 1503 for providing internet dataservices to mobile devices 1522-1524 and establishments 1542.

Base station device 1504 can be mounted on, or attached to, utility pole1516. In other embodiments, base station device 1504 can be neartransformers and/or other locations situated nearby a power line. Basestation device 1504 can facilitate connectivity to a mobile network formobile devices 1522 and 1524. Antennas 1512 and 1514, mounted on or nearutility poles 1518 and 1520, respectively, can receive signals from basestation device 1504 and transmit those signals to mobile devices 1522and 1524 over a much wider area than if the antennas 1512 and 1514 werelocated at or near base station device 1504.

It is noted that FIG. 15 displays three utility poles, in each instanceof the distribution systems 1550 and 1560, with one base station device,for purposes of simplicity. In other embodiments, utility pole 1516 canhave more base station devices, and more utility poles with distributedantennas and/or tethered connections to establishments 1542.

A transmission device 1506, such as transmission device 101 or 102presented in conjunction with FIG. 1, can transmit a signal from basestation device 1504 to antennas 1512 and 1514 via utility or powerline(s) that connect the utility poles 1516, 1518, and 1520. To transmitthe signal, radio source and/or transmission device 1506 upconverts thesignal (e.g., via frequency mixing) from base station device 1504 orotherwise converts the signal from the base station device 1504 to amicrowave band signal and the transmission device 1506 launches amicrowave band wave that propagates as a guided wave traveling along theutility line or other wire as described in previous embodiments. Atutility pole 1518, another transmission device 1508 receives the guidedwave (and optionally can amplify it as needed or desired or operate as arepeater to receive it and regenerate it) and sends it forward as aguided wave on the utility line or other wire. The transmission device1508 can also extract a signal from the microwave band guided wave andshift it down in frequency or otherwise convert it to its originalcellular band frequency (e.g., 1.9 GHz or other defined cellularfrequency) or another cellular (or non-cellular) band frequency. Anantenna 1512 can wireless transmit the downshifted signal to mobiledevice 1522. The process can be repeated by transmission device 1510,antenna 1514 and mobile device 1524, as necessary or desirable.

Transmissions from mobile devices 1522 and 1524 can also be received byantennas 1512 and 1514 respectively. The transmission devices 1508 and1510 can upshift or otherwise convert the cellular band signals tomicrowave band and transmit the signals as guided wave (e.g., surfacewave or other electromagnetic wave) transmissions over the power line(s)to base station device 1504.

Media content received by the central office 1501 can be supplied to thesecond instance of the distribution system 1560 via the base stationdevice 1504 for distribution to mobile devices 1522 and establishments1542. The transmission device 1510 can be tethered to the establishments1542 by one or more wired connections or a wireless interface. The oneor more wired connections may include without limitation, a power line,a coaxial cable, a fiber cable, a twisted pair cable, a guided wavetransmission medium or other suitable wired mediums for distribution ofmedia content and/or for providing internet services. In an exampleembodiment, the wired connections from the transmission device 1510 canbe communicatively coupled to one or more very high bit rate digitalsubscriber line (VDSL) modems located at one or more correspondingservice area interfaces (SAIs—not shown) or pedestals, each SAI orpedestal providing services to a portion of the establishments 1542. TheVDSL modems can be used to selectively distribute media content and/orprovide internet services to gateways (not shown) located in theestablishments 1542. The SAIs or pedestals can also be communicativelycoupled to the establishments 1542 over a wired medium such as a powerline, a coaxial cable, a fiber cable, a twisted pair cable, a guidedwave transmission medium or other suitable wired mediums. In otherexample embodiments, the transmission device 1510 can be communicativelycoupled directly to establishments 1542 without intermediate interfacessuch as the SAIs or pedestals.

In another example embodiment, system 1500 can employ diversity paths,where two or more utility lines or other wires are strung between theutility poles 1516, 1518, and 1520 (e.g., for example, two or more wiresbetween poles 1516 and 1520) and redundant transmissions from basestation/macrocell site 1502 are transmitted as guided waves down thesurface of the utility lines or other wires. The utility lines or otherwires can be either insulated or uninsulated, and depending on theenvironmental conditions that cause transmission losses, the couplingdevices can selectively receive signals from the insulated oruninsulated utility lines or other wires. The selection can be based onmeasurements of the signal-to-noise ratio of the wires, or based ondetermined weather/environmental conditions (e.g., moisture detectors,weather forecasts, etc.). The use of diversity paths with system 1500can enable alternate routing capabilities, load balancing, increasedload handling, concurrent bi-directional or synchronous communications,spread spectrum communications, etc.

It is noted that the use of the transmission devices 1506, 1508, and1510 in FIG. 15 are by way of example only, and that in otherembodiments, other uses are possible. For instance, transmission devicescan be used in a backhaul communication system, providing networkconnectivity to base station devices. Transmission devices 1506, 1508,and 1510 can be used in many circumstances where it is desirable totransmit guided wave communications over a wire, whether insulated ornot insulated. Transmission devices 1506, 1508, and 1510 areimprovements over other coupling devices due to no contact or limitedphysical and/or electrical contact with the wires that may carry highvoltages. The transmission device can be located away from the wire(e.g., spaced apart from the wire) and/or located on the wire so long asit is not electrically in contact with the wire, as the dielectric actsas an insulator, allowing for cheap, easy, and/or less complexinstallation. However, as previously noted conducting or non-dielectriccouplers can be employed, for example in configurations where the wirescorrespond to a telephone network, cable television network, broadbanddata service, fiber optic communications system or other networkemploying low voltages or having insulated transmission lines.

It is further noted, that while base station device 1504 and macrocellsite 1502 are illustrated in an embodiment, other network configurationsare likewise possible. For example, devices such as access points orother wireless gateways can be employed in a similar fashion to extendthe reach of other networks such as a wireless local area network, awireless personal area network or other wireless network that operatesin accordance with a communication protocol such as a 802.11 protocol,WIMAX protocol, UltraWideband protocol, BLUETOOTH® protocol, ZIGBEE®protocol or other wireless protocol.

Referring now to FIGS. 16A & 16B, block diagrams illustrating anexample, non-limiting embodiment of a system for managing a power gridcommunication system are shown. Considering FIG. 16A, a waveguide system1602 is presented for use in a guided wave communications system, suchas the system presented in conjunction with FIG. 15. The waveguidesystem 1602 can comprise sensors 1604, a power management system 1605, atransmission device 101 or 102 that includes at least one communicationinterface 205, transceiver 210 and coupler 220.

The waveguide system 1602 can be coupled to a power line 1610 forfacilitating guided wave communications in accordance with embodimentsdescribed in the subject disclosure. In an example embodiment, thetransmission device 101 or 102 includes coupler 220 for inducingelectromagnetic waves on a surface of the power line 1610 thatlongitudinally propagate along the surface of the power line 1610 asdescribed in the subject disclosure. The transmission device 101 or 102can also serve as a repeater for retransmitting electromagnetic waves onthe same power line 1610 or for routing electromagnetic waves betweenpower lines 1610 as shown in FIGS. 12-13.

The transmission device 101 or 102 includes transceiver 210 configuredto, for example, up-convert a signal operating at an original frequencyrange to electromagnetic waves operating at, exhibiting, or associatedwith a carrier frequency that propagate along a coupler to inducecorresponding guided electromagnetic waves that propagate along asurface of the power line 1610. A carrier frequency can be representedby a center frequency having upper and lower cutoff frequencies thatdefine the bandwidth of the electromagnetic waves. The power line 1610can be a wire (e.g., single stranded or multi-stranded) having aconducting surface or insulated surface. The transceiver 210 can alsoreceive signals from the coupler 220 and down-convert theelectromagnetic waves operating at a carrier frequency to signals attheir original frequency.

Signals received by the communications interface 205 of transmissiondevice 101 or 102 for up-conversion can include without limitationsignals supplied by a central office 1611 over a wired or wirelessinterface of the communications interface 205, a base station 1614 overa wired or wireless interface of the communications interface 205,wireless signals transmitted by mobile devices 1620 to the base station1614 for delivery over the wired or wireless interface of thecommunications interface 205, signals supplied by in-buildingcommunication devices 1618 over the wired or wireless interface of thecommunications interface 205, and/or wireless signals supplied to thecommunications interface 205 by mobile devices 1612 roaming in awireless communication range of the communications interface 205. Inembodiments where the waveguide system 1602 functions as a repeater,such as shown in FIGS. 12-13, the communications interface 205 may ormay not be included in the waveguide system 1602.

The electromagnetic waves propagating along the surface of the powerline 1610 can be modulated and formatted to include packets or frames ofdata that include a data payload and further include networkinginformation (such as header information for identifying one or moredestination waveguide systems 1602). The networking information may beprovided by the waveguide system 1602 or an originating device such asthe central office 1611, the base station 1614, mobile devices 1620, orin-building devices 1618, or a combination thereof. Additionally, themodulated electromagnetic waves can include error correction data formitigating signal disturbances. The networking information and errorcorrection data can be used by a destination waveguide system 1602 fordetecting transmissions directed to it, and for down-converting andprocessing with error correction data transmissions that include voiceand/or data signals directed to recipient communication devicescommunicatively coupled to the destination waveguide system 1602.

Referring now to the sensors 1604 of the waveguide system 1602, thesensors 1604 can comprise one or more of a temperature sensor 1604 a, adisturbance detection sensor 1604 b, a loss of energy sensor 1604 c, anoise sensor 1604 d, a vibration sensor 1604 e, an environmental (e.g.,weather) sensor 1604 f, and/or an image sensor 1604 g. The temperaturesensor 1604 a can be used to measure ambient temperature, a temperatureof the transmission device 101 or 102, a temperature of the power line1610, temperature differentials (e.g., compared to a setpoint orbaseline, between transmission device 101 or 102 and 1610, etc.), or anycombination thereof. In one embodiment, temperature metrics can becollected and reported periodically to a network management system 1601by way of the base station 1614.

The disturbance detection sensor 1604 b can perform measurements on thepower line 1610 to detect disturbances such as signal reflections, whichmay indicate a presence of a downstream disturbance that may impede thepropagation of electromagnetic waves on the power line 1610. A signalreflection can represent a distortion resulting from, for example, anelectromagnetic wave transmitted on the power line 1610 by thetransmission device 101 or 102 that reflects in whole or in part back tothe transmission device 101 or 102 from a disturbance in the power line1610 located downstream from the transmission device 101 or 102.

Signal reflections can be caused by obstructions on the power line 1610.For example, a tree limb may cause electromagnetic wave reflections whenthe tree limb is lying on the power line 1610, or is in close proximityto the power line 1610 which may cause a corona discharge. Otherobstructions that can cause electromagnetic wave reflections can includewithout limitation an object that has been entangled on the power line1610 (e.g., clothing, a shoe wrapped around a power line 1610 with ashoe string, etc.), a corroded build-up on the power line 1610 or an icebuild-up. Power grid components may also impede or obstruct with thepropagation of electromagnetic waves on the surface of power lines 1610.Illustrations of power grid components that may cause signal reflectionsinclude without limitation a transformer and a joint for connectingspliced power lines. A sharp angle on the power line 1610 may also causeelectromagnetic wave reflections.

The disturbance detection sensor 1604 b can comprise a circuit tocompare magnitudes of electromagnetic wave reflections to magnitudes oforiginal electromagnetic waves transmitted by the transmission device101 or 102 to determine how much a downstream disturbance in the powerline 1610 attenuates transmissions. The disturbance detection sensor1604 b can further comprise a spectral analyzer circuit for performingspectral analysis on the reflected waves. The spectral data generated bythe spectral analyzer circuit can be compared with spectral profiles viapattern recognition, an expert system, curve fitting, matched filteringor other artificial intelligence, classification or comparison techniqueto identify a type of disturbance based on, for example, the spectralprofile that most closely matches the spectral data. The spectralprofiles can be stored in a memory of the disturbance detection sensor1604 b or may be remotely accessible by the disturbance detection sensor1604 b. The profiles can comprise spectral data that models differentdisturbances that may be encountered on power lines 1610 to enable thedisturbance detection sensor 1604 b to identify disturbances locally. Anidentification of the disturbance if known can be reported to thenetwork management system 1601 by way of the base station 1614. Thedisturbance detection sensor 1604 b can also utilize the transmissiondevice 101 or 102 to transmit electromagnetic waves as test signals todetermine a roundtrip time for an electromagnetic wave reflection. Theround trip time measured by the disturbance detection sensor 1604 b canbe used to calculate a distance traveled by the electromagnetic wave upto a point where the reflection takes place, which enables thedisturbance detection sensor 1604 b to calculate a distance from thetransmission device 101 or 102 to the downstream disturbance on thepower line 1610.

The distance calculated can be reported to the network management system1601 by way of the base station 1614. In one embodiment, the location ofthe waveguide system 1602 on the power line 1610 may be known to thenetwork management system 1601, which the network management system 1601can use to determine a location of the disturbance on the power line1610 based on a known topology of the power grid. In another embodiment,the waveguide system 1602 can provide its location to the networkmanagement system 1601 to assist in the determination of the location ofthe disturbance on the power line 1610. The location of the waveguidesystem 1602 can be obtained by the waveguide system 1602 from apre-programmed location of the waveguide system 1602 stored in a memoryof the waveguide system 1602, or the waveguide system 1602 can determineits location using a GPS receiver (not shown) included in the waveguidesystem 1602.

The power management system 1605 provides energy to the aforementionedcomponents of the waveguide system 1602. The power management system1605 can receive energy from solar cells, or from a transformer (notshown) coupled to the power line 1610, or by inductive coupling to thepower line 1610 or another nearby power line. The power managementsystem 1605 can also include a backup battery and/or a super capacitoror other capacitor circuit for providing the waveguide system 1602 withtemporary power. The loss of energy sensor 1604 c can be used to detectwhen the waveguide system 1602 has a loss of power condition and/or theoccurrence of some other malfunction. For example, the loss of energysensor 1604 c can detect when there is a loss of power due to defectivesolar cells, an obstruction on the solar cells that causes them tomalfunction, loss of power on the power line 1610, and/or when thebackup power system malfunctions due to expiration of a backup battery,or a detectable defect in a super capacitor. When a malfunction and/orloss of power occurs, the loss of energy sensor 1604 c can notify thenetwork management system 1601 by way of the base station 1614.

The noise sensor 1604 d can be used to measure noise on the power line1610 that may adversely affect transmission of electromagnetic waves onthe power line 1610. The noise sensor 1604 d can sense unexpectedelectromagnetic interference, noise bursts, or other sources ofdisturbances that may interrupt reception of modulated electromagneticwaves on a surface of a power line 1610. A noise burst can be caused by,for example, a corona discharge, or other source of noise. The noisesensor 1604 d can compare the measured noise to a noise profile obtainedby the waveguide system 1602 from an internal database of noise profilesor from a remotely located database that stores noise profiles viapattern recognition, an expert system, curve fitting, matched filteringor other artificial intelligence, classification or comparisontechnique. From the comparison, the noise sensor 1604 d may identify anoise source (e.g., corona discharge or otherwise) based on, forexample, the noise profile that provides the closest match to themeasured noise. The noise sensor 1604 d can also detect how noiseaffects transmissions by measuring transmission metrics such as biterror rate, packet loss rate, jitter, packet retransmission requests,etc. The noise sensor 1604 d can report to the network management system1601 by way of the base station 1614 the identity of noise sources,their time of occurrence, and transmission metrics, among other things.

The vibration sensor 1604 e can include accelerometers and/or gyroscopesto detect 2D or 3D vibrations on the power line 1610. The vibrations canbe compared to vibration profiles that can be stored locally in thewaveguide system 1602, or obtained by the waveguide system 1602 from aremote database via pattern recognition, an expert system, curvefitting, matched filtering or other artificial intelligence,classification or comparison technique. Vibration profiles can be used,for example, to distinguish fallen trees from wind gusts based on, forexample, the vibration profile that provides the closest match to themeasured vibrations. The results of this analysis can be reported by thevibration sensor 1604 e to the network management system 1601 by way ofthe base station 1614.

The environmental sensor 1604 f can include a barometer for measuringatmospheric pressure, ambient temperature (which can be provided by thetemperature sensor 1604 a), wind speed, humidity, wind direction, andrainfall, among other things. The environmental sensor 1604 f cancollect raw information and process this information by comparing it toenvironmental profiles that can be obtained from a memory of thewaveguide system 1602 or a remote database to predict weather conditionsbefore they arise via pattern recognition, an expert system,knowledge-based system or other artificial intelligence, classificationor other weather modeling and prediction technique. The environmentalsensor 1604 f can report raw data as well as its analysis to the networkmanagement system 1601.

The image sensor 1604 g can be a digital camera (e.g., a charged coupleddevice or CCD imager, infrared camera, etc.) for capturing images in avicinity of the waveguide system 1602. The image sensor 1604 g caninclude an electromechanical mechanism to control movement (e.g., actualposition or focal points/zooms) of the camera for inspecting the powerline 1610 from multiple perspectives (e.g., top surface, bottom surface,left surface, right surface and so on). Alternatively, the image sensor1604 g can be designed such that no electromechanical mechanism isneeded in order to obtain the multiple perspectives. The collection andretrieval of imaging data generated by the image sensor 1604 g can becontrolled by the network management system 1601, or can be autonomouslycollected and reported by the image sensor 1604 g to the networkmanagement system 1601.

Other sensors that may be suitable for collecting telemetry informationassociated with the waveguide system 1602 and/or the power lines 1610for purposes of detecting, predicting and/or mitigating disturbancesthat can impede the propagation of electromagnetic wave transmissions onpower lines 1610 (or any other form of a transmission medium ofelectromagnetic waves) may be utilized by the waveguide system 1602.

Referring now to FIG. 16B, block diagram 1650 illustrates an example,non-limiting embodiment of a system for managing a power grid 1653 and acommunication system 1655 embedded therein or associated therewith inaccordance with various aspects described herein. The communicationsystem 1655 comprises a plurality of waveguide systems 1602 coupled topower lines 1610 of the power grid 1653. At least a portion of thewaveguide systems 1602 used in the communication system 1655 can be indirect communication with a base station 1614 and/or the networkmanagement system 1601. Waveguide systems 1602 not directly connected toa base station 1614 or the network management system 1601 can engage incommunication sessions with either a base station 1614 or the networkmanagement system 1601 by way of other downstream waveguide systems 1602connected to a base station 1614 or the network management system 1601.

The network management system 1601 can be communicatively coupled toequipment of a utility company 1652 and equipment of a communicationsservice provider 1654 for providing each entity, status informationassociated with the power grid 1653 and the communication system 1655,respectively. The network management system 1601, the equipment of theutility company 1652, and the communications service provider 1654 canaccess communication devices utilized by utility company personnel 1656and/or communication devices utilized by communications service providerpersonnel 1658 for purposes of providing status information and/or fordirecting such personnel in the management of the power grid 1653 and/orcommunication system 1655.

FIG. 17A illustrates a flow diagram of an example, non-limitingembodiment of a method 1700 for detecting and mitigating disturbancesoccurring in a communication network of the systems of FIGS. 16A & 16B.Method 1700 can begin with step 1702 where a waveguide system 1602transmits and receives messages embedded in, or forming part of,modulated electromagnetic waves or another type of electromagnetic wavestraveling along a surface of a power line 1610. The messages can bevoice messages, streaming video, and/or other data/information exchangedbetween communication devices communicatively coupled to thecommunication system 1655. At step 1704 the sensors 1604 of thewaveguide system 1602 can collect sensing data. In an embodiment, thesensing data can be collected in step 1704 prior to, during, or afterthe transmission and/or receipt of messages in step 1702. At step 1706the waveguide system 1602 (or the sensors 1604 themselves) can determinefrom the sensing data an actual or predicted occurrence of a disturbancein the communication system 1655 that can affect communicationsoriginating from (e.g., transmitted by) or received by the waveguidesystem 1602. The waveguide system 1602 (or the sensors 1604) can processtemperature data, signal reflection data, loss of energy data, noisedata, vibration data, environmental data, or any combination thereof tomake this determination. The waveguide system 1602 (or the sensors 1604)may also detect, identify, estimate, or predict the source of thedisturbance and/or its location in the communication system 1655. If adisturbance is neither detected/identified nor predicted/estimated atstep 1708, the waveguide system 1602 can proceed to step 1702 where itcontinues to transmit and receive messages embedded in, or forming partof, modulated electromagnetic waves traveling along a surface of thepower line 1610.

If at step 1708 a disturbance is detected/identified orpredicted/estimated to occur, the waveguide system 1602 proceeds to step1710 to determine if the disturbance adversely affects (oralternatively, is likely to adversely affect or the extent to which itmay adversely affect) transmission or reception of messages in thecommunication system 1655. In one embodiment, a duration threshold and afrequency of occurrence threshold can be used at step 1710 to determinewhen a disturbance adversely affects communications in the communicationsystem 1655. For illustration purposes only, assume a duration thresholdis set to 500 ms, while a frequency of occurrence threshold is set to 5disturbances occurring in an observation period of 10 sec. Thus, adisturbance having a duration greater than 500 ms will trigger theduration threshold. Additionally, any disturbance occurring more than 5times in a 10 sec time interval will trigger the frequency of occurrencethreshold.

In one embodiment, a disturbance may be considered to adversely affectsignal integrity in the communication systems 1655 when the durationthreshold alone is exceeded. In another embodiment, a disturbance may beconsidered as adversely affecting signal integrity in the communicationsystems 1655 when both the duration threshold and the frequency ofoccurrence threshold are exceeded. The latter embodiment is thus moreconservative than the former embodiment for classifying disturbancesthat adversely affect signal integrity in the communication system 1655.It will be appreciated that many other algorithms and associatedparameters and thresholds can be utilized for step 1710 in accordancewith example embodiments.

Referring back to method 1700, if at step 1710 the disturbance detectedat step 1708 does not (“No” in FIG. 17A) meet the condition foradversely affected communications (e.g., neither exceeds the durationthreshold nor the frequency of occurrence threshold), the waveguidesystem 1602 may proceed to step 1702 and continue processing messages.For instance, if the disturbance detected in step 1708 has a duration of1 msec with a single occurrence in a 10 sec time period, then neitherthreshold will be exceeded. Consequently, such a disturbance may beconsidered as having a nominal effect on signal integrity in thecommunication system 1655 and thus would not be flagged as a disturbancerequiring mitigation. Although not flagged, the occurrence of thedisturbance, its time of occurrence, its frequency of occurrence,spectral data, and/or other useful information, may be reported to thenetwork management system 1601 as telemetry data for monitoringpurposes.

Referring back to step 1710, if on the other hand the disturbancesatisfies the condition for adversely affected communications (e.g.,exceeds either or both thresholds), the waveguide system 1602 canproceed to step 1712 and report the incident to the network managementsystem 1601. The report can include raw sensing data collected by thesensors 1604, a description of the disturbance if known by the waveguidesystem 1602, a time of occurrence of the disturbance, a frequency ofoccurrence of the disturbance, a location associated with thedisturbance, parameters readings such as bit error rate, packet lossrate, retransmission requests, jitter, latency and so on. If thedisturbance is based on a prediction by one or more sensors of thewaveguide system 1602, the report can include a type of disturbanceexpected, and if predictable, an expected time occurrence of thedisturbance, and an expected frequency of occurrence of the predicteddisturbance when the prediction is based on historical sensing datacollected by the sensors 1604 of the waveguide system 1602.

At step 1714, the network management system 1601 can determine amitigation, circumvention, or correction technique, which may includedirecting the waveguide system 1602 to reroute traffic to circumvent thedisturbance if the location of the disturbance can be determined. In oneembodiment, the waveguide coupling device 1402 detecting the disturbancemay direct a repeater such as the one shown in FIGS. 13-14 to connectthe waveguide system 1602 from a primary power line affected by thedisturbance to a secondary power line to enable the waveguide system1602 to reroute traffic to a different transmission medium and avoid thedisturbance. In an embodiment where the waveguide system 1602 isconfigured as a repeater the waveguide system 1602 can itself performthe rerouting of traffic from the primary power line to the secondarypower line. It is further noted that for bidirectional communications(e.g., full or half-duplex communications), the repeater can beconfigured to reroute traffic from the secondary power line back to theprimary power line for processing by the waveguide system 1602.

In another embodiment, the waveguide system 1602 can redirect traffic byinstructing a first repeater situated upstream of the disturbance and asecond repeater situated downstream of the disturbance to redirecttraffic from a primary power line temporarily to a secondary power lineand back to the primary power line in a manner that avoids thedisturbance. It is further noted that for bidirectional communications(e.g., full or half-duplex communications), repeaters can be configuredto reroute traffic from the secondary power line back to the primarypower line.

To avoid interrupting existing communication sessions occurring on asecondary power line, the network management system 1601 may direct thewaveguide system 1602 to instruct repeater(s) to utilize unused timeslot(s) and/or frequency band(s) of the secondary power line forredirecting data and/or voice traffic away from the primary power lineto circumvent the disturbance.

At step 1716, while traffic is being rerouted to avoid the disturbance,the network management system 1601 can notify equipment of the utilitycompany 1652 and/or equipment of the communications service provider1654, which in turn may notify personnel of the utility company 1656and/or personnel of the communications service provider 1658 of thedetected disturbance and its location if known. Field personnel fromeither party can attend to resolving the disturbance at a determinedlocation of the disturbance. Once the disturbance is removed orotherwise mitigated by personnel of the utility company and/or personnelof the communications service provider, such personnel can notify theirrespective companies and/or the network management system 1601 utilizingfield equipment (e.g., a laptop computer, smartphone, etc.)communicatively coupled to network management system 1601, and/orequipment of the utility company and/or the communications serviceprovider. The notification can include a description of how thedisturbance was mitigated and any changes to the power lines 1610 thatmay change a topology of the communication system 1655.

Once the disturbance has been resolved (as determined in decision 1718),the network management system 1601 can direct the waveguide system 1602at step 1720 to restore the previous routing configuration used by thewaveguide system 1602 or route traffic according to a new routingconfiguration if the restoration strategy used to mitigate thedisturbance resulted in a new network topology of the communicationsystem 1655 (in the alternative, if the decision is “No” at step 1718,step 1718 is repeated as shown in FIG. 17A). In another embodiment, thewaveguide system 1602 can be configured to monitor mitigation of thedisturbance by transmitting test signals on the power line 1610 todetermine when the disturbance has been removed. Once the waveguidesystem 1602 detects an absence of the disturbance it can autonomouslyrestore its routing configuration without assistance by the networkmanagement system 1601 if it determines the network topology of thecommunication system 1655 has not changed, or it can utilize a newrouting configuration that adapts to a detected new network topology.

FIG. 17B illustrates a flow diagram of an example, non-limitingembodiment of a method 1750 for detecting and mitigating disturbancesoccurring in a communication network of the system of FIGS. 16A and 16B.In one embodiment, method 1750 can begin with step 1752 where a networkmanagement system 1601 receives from equipment of the utility company1652 or equipment of the communications service provider 1654maintenance information associated with a maintenance schedule. Thenetwork management system 1601 can at step 1754 identify from themaintenance information, maintenance activities to be performed duringthe maintenance schedule. From these activities, the network managementsystem 1601 can detect a disturbance resulting from the maintenance(e.g., scheduled replacement of a power line 1610, scheduled replacementof a waveguide system 1602 on the power line 1610, scheduledreconfiguration of power lines 1610 in the power grid 1653, etc.).

In another embodiment, the network management system 1601 can receive atstep 1755 telemetry information from one or more waveguide systems 1602.The telemetry information can include among other things an identity ofeach waveguide system 1602 submitting the telemetry information,measurements taken by sensors 1604 of each waveguide system 1602,information relating to predicted, estimated, or actual disturbancesdetected by the sensors 1604 of each waveguide system 1602, locationinformation associated with each waveguide system 1602, an estimatedlocation of a detected disturbance, an identification of thedisturbance, and so on. The network management system 1601 can determinefrom the telemetry information a type of disturbance that may be adverseto operations of the waveguide, transmission of the electromagneticwaves along the wire surface, or both. The network management system1601 can also use telemetry information from multiple waveguide systems1602 to isolate and identify the disturbance. Additionally, the networkmanagement system 1601 can request telemetry information from waveguidesystems 1602 in a vicinity of an affected waveguide system 1602 totriangulate a location of the disturbance and/or validate anidentification of the disturbance by receiving similar telemetryinformation from other waveguide systems 1602.

In yet another embodiment, the network management system 1601 canreceive at step 1756 an unscheduled activity report from maintenancefield personnel. Unscheduled maintenance may occur as result of fieldcalls that are unplanned or as a result of unexpected field issuesdiscovered during field calls or scheduled maintenance activities. Theactivity report can identify changes to a topology configuration of thepower grid 1653 resulting from field personnel addressing discoveredissues in the communication system 1655 and/or power grid 1653, changesto one or more waveguide systems 1602 (such as replacement or repairthereof), mitigation of disturbances performed if any, and so on.

At step 1758, the network management system 1601 can determine fromreports received according to steps 1752 through 1756 if a disturbancewill occur based on a maintenance schedule, or if a disturbance hasoccurred or is predicted to occur based on telemetry data, or if adisturbance has occurred due to an unplanned maintenance identified in afield activity report. From any of these reports, the network managementsystem 1601 can determine whether a detected or predicted disturbancerequires rerouting of traffic by the affected waveguide systems 1602 orother waveguide systems 1602 of the communication system 1655.

When a disturbance is detected or predicted at step 1758, the networkmanagement system 1601 can proceed to step 1760 where it can direct oneor more waveguide systems 1602 to reroute traffic to circumvent thedisturbance (in the alternative, if the decision is “No” at step 1758,step 1758 is repeated as shown in FIG. 17B). When the disturbance ispermanent due to a permanent topology change of the power grid 1653, thenetwork management system 1601 can proceed to step 1770 and skip steps1762, 1764, 1766, and 1772. At step 1770, the network management system1601 can direct one or more waveguide systems 1602 to use a new routingconfiguration that adapts to the new topology. However, when thedisturbance has been detected from telemetry information supplied by oneor more waveguide systems 1602, the network management system 1601 cannotify maintenance personnel of the utility company 1656 or thecommunications service provider 1658 of a location of the disturbance, atype of disturbance if known, and related information that may behelpful to such personnel to mitigate the disturbance. When adisturbance is expected due to maintenance activities, the networkmanagement system 1601 can direct one or more waveguide systems 1602 toreconfigure traffic routes at a given schedule (consistent with themaintenance schedule) to avoid disturbances caused by the maintenanceactivities during the maintenance schedule.

Returning back to step 1760 and upon its completion, the process cancontinue with step 1762. At step 1762, the network management system1601 can monitor when the disturbance(s) have been mitigated by fieldpersonnel. Mitigation of a disturbance can be detected at step 1762 byanalyzing field reports submitted to the network management system 1601by field personnel over a communications network (e.g., cellularcommunication system) utilizing field equipment (e.g., a laptop computeror handheld computer/device). If field personnel have reported that adisturbance has been mitigated, the network management system 1601 canproceed to step 1764 to determine from the field report whether atopology change was required to mitigate the disturbance (in thealternative, if the decision is “No” at step 1762, step 1762 is repeatedas shown in FIG. 17B). A topology change can include rerouting a powerline 1610, reconfiguring a waveguide system 1602 to utilize a differentpower line 1610, otherwise utilizing an alternative link to bypass thedisturbance and so on. If a topology change has taken place, the networkmanagement system 1601 can direct at step 1770 one or more waveguidesystems 1602 to use a new routing configuration that adapts to the newtopology.

If, however, a topology change has not been reported by field personnel,the network management system 1601 can proceed to step 1766 where it candirect one or more waveguide systems 1602 to send test signals to test arouting configuration that had been used prior to the detecteddisturbance(s). Test signals can be sent to affected waveguide systems1602 in a vicinity of the disturbance. The test signals can be used todetermine if signal disturbances (e.g., electromagnetic wavereflections) are detected by any of the waveguide systems 1602. If thetest signals confirm that a prior routing configuration is no longersubject to previously detected disturbance(s), then the networkmanagement system 1601 can at step 1772 direct the affected waveguidesystems 1602 to restore a previous routing configuration. If, however,test signals analyzed by one or more waveguide coupling device 1402 andreported to the network management system 1601 indicate that thedisturbance(s) or new disturbance(s) are present, then the networkmanagement system 1601 will proceed to step 1768 and report thisinformation to field personnel to further address field issues. Thenetwork management system 1601 can in this situation continue to monitormitigation of the disturbance(s) at step 1762.

In the aforementioned embodiments, the waveguide systems 1602 can beconfigured to be self-adapting to changes in the power grid 1653 and/orto mitigation of disturbances. That is, one or more affected waveguidesystems 1602 can be configured to self-monitor mitigation ofdisturbances and reconfigure traffic routes without requiringinstructions to be sent to them by the network management system 1601.In this embodiment, the one or more waveguide systems 1602 that areself-configurable can inform the network management system 1601 of itsrouting choices so that the network management system 1601 can maintaina macro-level view of the communication topology of the communicationsystem 1655.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIGS. 17A and17B, respectively, it is to be understood and appreciated that theclaimed subject matter is not limited by the order of the blocks, assome blocks may occur in different orders and/or concurrently with otherblocks from what is depicted and described herein. Moreover, not allillustrated blocks may be required to implement the methods describedherein.

Turning now to FIG. 18A, a block diagram illustrating an example,non-limiting embodiment of a transmission medium 1800 for propagatingguided electromagnetic waves is shown. In particular, a further exampleof transmission medium 125 presented in conjunction with FIG. 1 ispresented. In an embodiment, the transmission medium 1800 can comprise afirst dielectric material 1802 and a second dielectric material 1804disposed thereon. In an embodiment, the first dielectric material 1802can comprise a dielectric core (referred to herein as dielectric core1802; in the example shown in FIG. 18A, this can comprise a Dielectricrod (e.g., HDPE 2-3 mm diameter) and the second dielectric material 1804can comprise a cladding or shell such as a dielectric foam thatsurrounds in whole or in part the dielectric core (referred to herein asdielectric foam 1804). In an embodiment, the dielectric core 1802 anddielectric foam 1804 can be coaxially aligned to each other (althoughnot necessary). In an embodiment, the combination of the dielectric core1802 and the dielectric foam 1804 can be flexed or bent at least by 45degrees without damaging the materials of the dielectric core 1802 andthe dielectric foam 1804. In an embodiment, an outer surface of thedielectric foam 1804 can be further surrounded in whole or in part by athird dielectric material 1806, which can serve as an outer jacket(referred to herein as jacket 1806). The jacket 1806 can preventexposure of the dielectric core 1802 and the dielectric foam 1804 to anenvironment that can adversely affect the propagation of electromagneticwaves (e.g., water, soil, etc.).

The dielectric core 1802 can comprise, for example, a high densitypolyethylene material (i.e., HDPE), a high density polyurethanematerial, or other suitable dielectric material(s). The dielectric foam1804 can comprise, for example, a cellular plastic material such anexpanded polyethylene material (i.e., EPE), or other suitable dielectricmaterial(s). The jacket 1806 can comprise, for example, a polyethylenematerial or equivalent. In an embodiment, the dielectric constant of thedielectric foam 1804 can be (or substantially) lower than the dielectricconstant of the dielectric core 1802. For example, the dielectricconstant of the dielectric core 1802 can be approximately 2.3 while thedielectric constant of the dielectric foam 1804 can be approximately1.15 (slightly higher than the dielectric constant of air).

The dielectric core 1802 can be used for receiving signals in the formof electromagnetic waves from a launcher or other coupling devicedescribed herein which can be configured to launch guidedelectromagnetic waves on the transmission medium 1800. In oneembodiment, the transmission medium 1800 can be coupled to a hollowwaveguide 1808 structured as, for example, a circular waveguide 1809,which can receive electromagnetic waves from a radiating device such asa stub antenna (not shown). The hollow waveguide 1808 can in turn induceguided electromagnetic waves in the dielectric core 1802. In thisconfiguration, the guided electromagnetic waves are guided by or boundto the dielectric core 1802 and propagate longitudinally along thedielectric core 1802. By adjusting electronics associated with thelauncher, an operating frequency of the electromagnetic waves can bechosen such that an electric field intensity profile 1810 of the guidedelectromagnetic waves extends nominally (or not at all) outside of thejacket 1806.

By maintaining most (if not all) of the field strength of the guidedelectromagnetic waves within portions of the dielectric core 1802, thedielectric foam 1804 and/or the jacket 1806, the transmission medium1800 can be used in hostile environments without adversely affecting thepropagation of the electromagnetic waves propagating therein. Forexample, the transmission medium 1800 can be buried in soil with no (ornearly no) adverse effect to the guided electromagnetic wavespropagating in the transmission medium 1800. Similarly, the transmissionmedium 1800 can be exposed to water (e.g., rain or placed underwater)with no (or nearly no) adverse effect to the guided electromagneticwaves propagating in the transmission medium 1800. In an embodiment, thepropagation loss of guided electromagnetic waves in the foregoingembodiments can be 1 to 2 dB per meter or better at an operatingfrequency of 60 GHz. Depending on the operating frequency of the guidedelectromagnetic waves and/or the materials used for the transmissionmedium 1800 other propagation losses may be possible. Additionally,depending on the materials used to construct the transmission medium1800, the transmission medium 1800 can in some embodiments be flexedlaterally with no (or nearly no) adverse effect to the guidedelectromagnetic waves propagating through the dielectric core 1802 andthe dielectric foam 1804.

FIG. 18B depicts a transmission medium 1820 that differs from thetransmission medium 1800 of FIG. 18A, yet provides a further example ofthe transmission medium 125 presented in conjunction with FIG. 1. Thetransmission medium 1820 shows similar reference numerals for similarelements of the transmission medium 1800 of FIG. 18A. In contrast to thetransmission medium 1800, the transmission medium 1820 comprises aconductive core 1822 having an insulation layer 1823 surrounding theconductive core 1822 in whole or in part. The combination of theinsulation layer 1823 and the conductive core 1822 will be referred toherein as an insulated conductor 1825. In the illustration of FIG. 18B,the insulation layer 1823 is covered in whole or in part by a dielectricfoam 1804 and jacket 1806, which can be constructed from the materialspreviously described. In an embodiment, the insulation layer 1823 cancomprise a dielectric material, such as polyethylene, having a higherdielectric constant than the dielectric foam 1804 (e.g., 2.3 and 1.15,respectively). In an embodiment, the components of the transmissionmedium 1820 can be coaxially aligned (although not necessary). In anembodiment, a hollow waveguide 1808 having metal plates 1809, which canbe separated from the insulation layer 1823 (although not necessary) canbe used to launch guided electromagnetic waves that substantiallypropagate on an outer surface of the insulation layer 1823, howeverother coupling devices as described herein can likewise be employed. Inan embodiment, the guided electromagnetic waves can be sufficientlyguided by or bound by the insulation layer 1823 to guide theelectromagnetic waves longitudinally along the insulation layer 1823. Byadjusting operational parameters of the launcher, an operating frequencyof the guided electromagnetic waves launched by the hollow waveguide1808 can generate an electric field intensity profile 1824 that resultsin the guided electromagnetic waves being substantially confined withinthe dielectric foam 1804 thereby preventing the guided electromagneticwaves from being exposed to an environment (e.g., water, soil, etc.)that adversely affects propagation of the guided electromagnetic wavesvia the transmission medium 1820.

FIG. 18C depicts a transmission medium 1830 that differs from thetransmission mediums 1800 and 1820 of FIGS. 18A and 18B, yet provides afurther example of the transmission medium 125 presented in conjunctionwith FIG. 1. The transmission medium 1830 shows similar referencenumerals for similar elements of the transmission mediums 1800 and 1820of FIGS. 18A and 18B, respectively. In contrast to the transmissionmediums 1800 and 1820, the transmission medium 1830 comprises a bare (oruninsulated) conductor 1832 surrounded in whole or in part by thedielectric foam 1804 and the jacket 1806, which can be constructed fromthe materials previously described. In an embodiment, the components ofthe transmission medium 1830 can be coaxially aligned (although notnecessary). In an embodiment, a hollow waveguide 1808 having metalplates 1809 coupled to the bare conductor 1832 can be used to launchguided electromagnetic waves that substantially propagate on an outersurface of the bare conductor 1832, however other coupling devicesdescribed herein can likewise be employed. In an embodiment, the guidedelectromagnetic waves can be sufficiently guided by or bound by the bareconductor 1832 to guide the guided electromagnetic waves longitudinallyalong the bare conductor 1832. By adjusting operational parameters ofthe launcher, an operating frequency of the guided electromagnetic waveslaunched by the hollow waveguide 1808 can generate an electric fieldintensity profile 1834 that results in the guided electromagnetic wavesbeing substantially confined within the dielectric foam 1804 therebypreventing the guided electromagnetic waves from being exposed to anenvironment (e.g., water, soil, etc.) that adversely affects propagationof the electromagnetic waves via the transmission medium 1830.

It should be noted that the hollow waveguide 1808 used with thetransmission mediums 1800, 1820 and 1830 of FIGS. 18A, 18B and 18C,respectively, can be replaced with other launchers or coupling devices.Additionally, the propagation mode(s) of the electromagnetic waves forany of the foregoing embodiments can be fundamental mode(s), anon-fundamental (or asymmetric) mode(s), or combinations thereof.

FIG. 18D is a block diagram illustrating an example, non-limitingembodiment of bundled transmission media 1836 in accordance with variousaspects described herein. The bundled transmission media 1836 cancomprise a plurality of cables 1838 held in place by a flexible sleeve1839. The plurality of cables 1838 can comprise multiple instances ofcable 1800 of FIG. 18A, multiple instances of cable 1820 of FIG. 18B,multiple instances of cable 1830 of FIG. 18C, or any combinationsthereof. The sleeve 1839 can comprise a dielectric material thatprevents soil, water or other external materials from making contactwith the plurality of cables 1838. In an embodiment, a plurality oflaunchers, each utilizing a transceiver similar to the one depicted inFIG. 10A or other coupling devices described herein, can be adapted toselectively induce a guided electromagnetic wave in each cable, eachguided electromagnetic wave conveys different data (e.g., voice, video,messaging, content, etc.). In an embodiment, by adjusting operationalparameters of each launcher or other coupling device, the electric fieldintensity profile of each guided electromagnetic wave can be fully orsubstantially confined within layers of a corresponding cable 1838 toreduce cross-talk between cables 1838.

In situations where the electric field intensity profile of each guidedelectromagnetic wave is not fully or substantially confined within acorresponding cable 1838, cross-talk of electromagnetic signals canoccur between cables 1838 as illustrated by signal plots associated withtwo cables depicted in FIG. 18E. The plots in FIG. 18E show that when aguided electromagnetic wave is induced on a first cable, the emittedelectric and magnetic fields of the first cable can induce signals onthe second cable, which results in cross-talk. Several mitigationoptions can be used to reduce cross-talk between the cables 1838 of FIG.18D. In an embodiment, an absorption material 1840 that can absorbelectromagnetic fields, such as carbon, can be applied to the cables1838 as shown in FIG. 18F to polarize each guided electromagnetic waveat various polarization states to reduce cross-talk between cables 1838.In another embodiment (not shown), carbon beads can be added to gapsbetween the cables 1838 to reduce cross-talk.

In yet another embodiment (not shown), a diameter of cable 1838 can beconfigured differently to vary a speed of propagation of guidedelectromagnetic waves between the cables 1838 in order to reducecross-talk between cables 1838. In an embodiment (not shown), a shape ofeach cable 1838 can be made asymmetric (e.g., elliptical) to direct theguided electromagnetic fields of each cable 1838 away from each other toreduce cross-talk. In an embodiment (not shown), a filler material suchas dielectric foam can be added between cables 1838 to sufficientlyseparate the cables 1838 to reduce cross-talk therebetween. In anembodiment (not shown), longitudinal carbon strips or swirls can beapplied to on an outer surface of the jacket 1806 of each cable 1838 toreduce radiation of guided electromagnetic waves outside of the jacket1806 and thereby reduce cross-talk between cables 1838. In yet anotherembodiment, each launcher can be configured to launch a guidedelectromagnetic wave having a different frequency, modulation, wavepropagation mode, such as an orthogonal frequency, modulation or mode,to reduce cross-talk between the cables 1838.

In yet another embodiment (not shown), pairs of cables 1838 can betwisted in a helix to reduce cross-talk between the pairs and othercables 1838 in a vicinity of the pairs. In some embodiments, certaincables 1838 can be twisted while other cables 1838 are not twisted toreduce cross-talk between the cables 1838. Additionally, each twistedpair cable 1838 can have different pitches (i.e., different twist rates,such as twists per meter) to further reduce cross-talk between the pairsand other cables 1838 in a vicinity of the pairs. In another embodiment(not shown), launchers or other coupling devices can be configured toinduce guided electromagnetic waves in the cables 1838 havingelectromagnetic fields that extend beyond the jacket 1806 into gapsbetween the cables to reduce cross-talk between the cables 1838. It issubmitted that any one of the foregoing embodiments for mitigatingcross-talk between cables 1838 can be combined to further reducecross-talk therebetween.

FIGS. 18G and 18H are block diagrams illustrating example, non-limitingembodiments of a transmission medium with an inner waveguide inaccordance with various aspects described herein. In an embodiment, atransmission medium 1841 can comprise a core 1842. In one embodiment,the core 1842 can be a dielectric core 1842 (e.g., polyethylene). Inanother embodiment, the core 1842 can be an insulated or uninsulatedconductor. The core 1842 can be surrounded by a shell 1844 comprising adielectric foam (e.g., expanded polyethylene material) having a lowerdielectric constant than the dielectric constant of a dielectric core,or insulation layer of a conductive core. The difference in dielectricconstants enables electromagnetic waves to be bound and guided by thecore 1842. The shell 1844 can be covered by a shell jacket 1845. Theshell jacket 1845 can be made of rigid material (e.g., high densityplastic) or a high tensile strength material (e.g., synthetic fiber). Inan embodiment, the shell jacket 1845 can be used to prevent exposure ofthe shell 1844 and core 1842 from an adverse environment (e.g., water,moisture, soil, etc.). In an embodiment, the shell jacket 1845 can besufficiently rigid to separate an outer surface of the core 1842 from aninner surface of the shell jacket 1845 thereby resulting in alongitudinal gap between the shell jacket 1854 and the core 1842. Thelongitudinal gap can be filled with the dielectric foam of the shell1844.

The transmission medium 1841 can further include a plurality of outerring conductors 1846. The outer ring conductors 1846 can be strands ofconductive material that are woven around the shell jacket 1845, therebycovering the shell jacket 1845 in whole or in part. The outer ringconductors 1846 can serve the function of a power line having a returnelectrical path similar to the embodiments described in the subjectdisclosure for receiving power signals from a source (e.g., atransformer, a power generator, etc.). In one embodiment, the outer ringconductors 1846 can be covered by a cable jacket 1847 to preventexposure of the outer ring conductors 1846 to water, soil, or otherenvironmental factors. The cable jacket 1847 can be made of aninsulating material such as polyethylene. The core 1842 can be used as acenter waveguide for the propagation of electromagnetic waves. A hollowwaveguide launcher 1808, such as the circular waveguide previouslydescribed, can be used to launch signals that induce electromagneticwaves guided by the core 1842 in ways similar to those described for theembodiments of FIGS. 18A, 18B, and 18C. The electromagnetic waves can beguided by the core 1842 without utilizing the electrical return path ofthe outer ring conductors 1846 or any other electrical return path. Byadjusting electronics associated with the launcher 1808, an operatingfrequency of the electromagnetic waves can be chosen such that a fieldintensity profile of the guided electromagnetic waves extends nominally(or not at all) outside of the shell jacket 1845.

In another embodiment, a transmission medium 1843 can comprise a hollowcore 1842′ surrounded by a shell jacket 1845′. The shell jacket 1845′can have an inner conductive surface or other surface materials thatenable the hollow core 1842′ to be used as a conduit for electromagneticwaves. The shell jacket 1845′ can be covered at least in part with theouter ring conductors 1846 described earlier for conducting a powersignal. In an embodiment, a cable jacket 1847 can be disposed on anouter surface of the outer ring conductors 1846 to prevent exposure ofthe outer ring conductors 1846 to water, soil or other environmentalfactors. A waveguide launcher 1808 can be used to launch electromagneticwaves guided by the hollow core 1842′ and the conductive inner surfaceof the shell jacket 1845′. In an embodiment (not shown) the hollow core1842′ can further include a dielectric foam such as described earlier.

Transmission medium 1841 can represent a multi-purpose cable thatconducts power on the outer ring conductors 1846 utilizing an electricalreturn path and that provides communication services by way of an innerwaveguide comprising a combination of the core 1842, the shell 1844 andthe shell jacket 1845. The inner waveguide can be used for transmittingor receiving electromagnetic waves (without utilizing an electricalreturn path) guided by the core 1842. Similarly, transmission medium1843 can represent a multi-purpose cable that conducts power on theouter ring conductors 1846 utilizing an electrical return path and thatprovides communication services by way of an inner waveguide comprisinga combination of the hollow core 1842′ and the shell jacket 1845′. Theinner waveguide can be used for transmitting or receivingelectromagnetic waves (without utilizing an electrical return path)guided the hollow core 1842′ and the shell jacket 1845′.

It is submitted that embodiments of FIGS. 18G-18H can be adapted to usemultiple inner waveguides surrounded by outer ring conductors 1846. Theinner waveguides can be adapted to use to cross-talk mitigationtechniques described above (e.g., twisted pairs of waveguides,waveguides of different structural dimensions, use of polarizers withinthe shell, use of different wave modes, etc.).

For illustration purposes only, the transmission mediums 1800, 1820,1830 1836, 1841 and 1843 will be referred to herein as a cable 1850 withan understanding that cable 1850 can represent any one of thetransmission mediums described in the subject disclosure, or a bundlingof multiple instances thereof. For illustration purposes only, thedielectric core 1802, insulated conductor 1825, bare conductor 1832,core 1842, or hollow core 1842′ of the transmission mediums 1800, 1820,1830, 1836, 1841 and 1843, respectively, will be referred to herein astransmission core 1852 with an understanding that cable 1850 can utilizethe dielectric core 1802, insulated conductor 1825, bare conductor 1832,core 1842, or hollow core 1842′ of transmission mediums 1800, 1820,1830, 1836, 1841 and/or 1843, respectively.

Turning now to FIGS. 18I and 18J, block diagrams illustrating example,non-limiting embodiments of connector configurations that can be used bycable 1850 are shown. In one embodiment, cable 1850 can be configuredwith a female connection arrangement or a male connection arrangement asdepicted in FIG. 18I. The male configuration on the right of FIG. 18Ican be accomplished by stripping the dielectric foam 1804 (and jacket1806 if there is one) to expose a portion of the transmission core 1852.The female configuration on the left of FIG. 18I can be accomplished byremoving a portion of the transmission core 1852, while maintaining thedielectric foam 1804 (and jacket 1806 if there is one). In an embodimentin which the transmission core 1852 is hollow as described in relationto FIG. 18H, the male portion of the transmission core 1852 canrepresent a hollow core with a rigid outer surface that can slide intothe female arrangement on the left side of FIG. 18I to align the hollowcores together. It is further noted that in the embodiments of FIGS.18G-18H, the outer ring of conductors 1846 can be modified to connectmale and female portions of cable 1850.

Based on the aforementioned embodiments, the two cables 1850 having maleand female connector arrangements can be mated together. A sleeve withan adhesive inner lining or a shrink wrap material (not shown) can beapplied to an area of a joint between cables 1850 to maintain the jointin a fixed position and prevent exposure (e.g., to water, soil, etc.).When the cables 1850 are mated, the transmission core 1852 of one cablewill be in close proximity to the transmission core 1852 of the othercable. Guided electromagnetic waves propagating by way of either thetransmission core 1852 of cables 1850 traveling from either directioncan cross over between the disjoint the transmission cores 1852 whetheror not the transmission cores 1852 touch, whether or not thetransmission cores 1852 are coaxially aligned, and/or whether or notthere is a gap between the transmission cores 1852.

In another embodiment, a splicing device 1860 having female connectorarrangements at both ends can be used to mate cables 1850 having maleconnector arrangements as shown in FIG. 18J. In an alternativeembodiment not shown in FIG. 18J, the splicing device 1860 can beadapted to have male connector arrangements at both ends which can bemated to cables 1850 having female connector arrangements. In anotherembodiment not shown in FIG. 18J, the splicing device 1860 can beadapted to have a male connector arrangement and a female connectorarrangement at opposite ends which can be mated to cables 1850 havingfemale and male connector arrangements, respectively. It is furthernoted that for a transmission core 1852 having a hollow core, the maleand female arrangements described in FIG. 18I can be applied to thesplicing device 1860 whether the ends of the splicing device 1860 areboth male, both female, or a combination thereof.

The foregoing embodiments for connecting cables illustrated in FIGS.18I-18J can be applied to each single instance of cable 1838 of bundledtransmission media 1836. Similarly, the foregoing embodimentsillustrated in FIGS. 18I-18J can be applied to each single instance ofan inner waveguide for a cable 1841 or 1843 having multiple innerwaveguides.

Turning now to FIG. 18K, a block diagram illustrating example,non-limiting embodiments of transmission mediums 1800′, 1800″, 1800′″and 1800″″ for propagating guided electromagnetic waves is shown. In anembodiment, a transmission medium 1800′ can include a core 1801, and adielectric foam 1804′ divided into sections and covered by a jacket 1806as shown in FIG. 18K. The core 1801 can be represented by the dielectriccore 1802 of FIG. 18A, the insulated conductor 1825 of FIG. 18B, or thebare conductor 1832 of FIG. 18C. Each section of dielectric foam 1804′can be separated by a gap (e.g., air, gas, vacuum, or a substance with alow dielectric constant). In an embodiment, the gap separations betweenthe sections of dielectric foam 1804′ can be quasi-random as shown inFIG. 18K, which can be helpful in reducing reflections ofelectromagnetic waves occurring at each section of dielectric foam 1804′as they propagate longitudinally along the core 1801. The sections ofthe dielectric foam 1804′ can be constructed, for example, as washersmade of a dielectric foam having an inner opening for supporting thecore 1801 in a fixed position. For illustration purposes only, thewashers will be referred to herein as washers 1804′. In an embodiment,the inner opening of each washer 1804′ can be coaxially aligned with anaxis of the core 1801. In another embodiment, the inner opening of eachwasher 1804′ can be offset from the axis of the core 1801. In anotherembodiment (not shown), each washer 1804′ can have a variablelongitudinal thickness as shown by differences in thickness of thewashers 1804′.

In an alternative embodiment, a transmission medium 1800″ can include acore 1801, and a strip of dielectric foam 1804″ wrapped around the corein a helix covered by a jacket 1806 as shown in FIG. 18K. Although itmay not be apparent from the drawing shown in FIG. 18K, in an embodimentthe strip of dielectric foam 1804″ can be twisted around the core 1801with variable pitches (i.e., different twist rates) for differentsections of the strip of dielectric foam 1804″. Utilizing variablepitches can help reduce reflections or other disturbances of theelectromagnetic waves occurring between areas of the core 1801 notcovered by the strip of dielectric foam 1804″. It is further noted thatthe thickness (diameter) of the strip of dielectric foam 1804″ can besubstantially larger (e.g., 2 or more times larger) than diameter of thecore 1801 shown in FIG. 18K.

In an alternative embodiment, a transmission medium 1800′″ (shown in across-sectional view) can include a non-circular core 1801′ covered by adielectric foam 1804 and jacket 1806. In an embodiment, the non-circularcore 1801′ can have an elliptical structure as shown in FIG. 18K, orother suitable non-circular structure. In another embodiment, thenon-circular core 1801′ can have an asymmetric structure. A non-circularcore 1801′ can be used to polarize the fields of electromagnetic wavesinduced on the non-circular core 1801′. The structure of thenon-circular core 1801′ can help preserve the polarization of theelectromagnetic waves as they propagate along the non-circular core1801′.

In an alternative embodiment, a transmission medium 1800″″ (shown in across-sectional view) can include multiple cores 1801″ (only two coresare shown but more are possible). The multiple cores 1801″ can becovered by a dielectric foam 1804 and jacket 1806. The multiple cores1801″ can be used to polarize the fields of electromagnetic wavesinduced on the multiple cores 1801″. The structure of the multiple cores1801′ can preserve the polarization of the guided electromagnetic wavesas they propagate along the multiple cores 1801″.

It will be appreciated that the embodiments of FIG. 18K can be used tomodify the embodiments of FIGS. 18G-18H. For example, core 1842 or core1842′ can be adapted to utilized sectionalized shells 1804′ with gapstherebetween, or one or more strips of dielectric foam 1804″. Similarly,core 1842 or core 1842′ can be adapted to have a non-circular core 1801′that may have symmetric or asymmetric cross-sectional structure.Additionally, core 1842 or core 1842′ can be adapted to use multiplecores 1801″ in a single inner waveguide, or different numbers of coreswhen multiple inner waveguides are used. Accordingly, any of theembodiments shown in FIG. 18K can be applied singly or in combination tothe embodiments of 18G-18H.

Turning now to FIG. 18L is a block diagram illustrating example,non-limiting embodiments of bundled transmission media to mitigatecross-talk in accordance with various aspects described herein. In anembodiment, a bundled transmission medium 1836′ can include variablecore structures 1803. By varying the structures of cores 1803, fields ofguided electromagnetic waves induced in each of the cores oftransmission medium 1836′ may differ sufficiently to reduce cross-talkbetween cables 1838. In another embodiment, a bundled transmission media1836″ can include a variable number of cores 1803′ per cable 1838. Byvarying the number of cores 1803′ per cable 1838, fields of guidedelectromagnetic waves induced in the one or more cores of transmissionmedium 1836″ may differ sufficiently to reduce cross-talk between cables1838. In another embodiment, the cores 1803 or 1803′ can be of differentmaterials. For example, the cores 1803 or 1803′ can be a dielectric core1802, an insulated conductor core 1825, a bare conductor core 1832, orany combinations thereof.

It is noted that the embodiments illustrated in FIGS. 18A-18D and18F-18H can be modified by and/or combined with some of the embodimentsof FIGS. 18K-18L. It is further noted that one or more of theembodiments illustrated in FIGS. 18K-18L can be combined (e.g., usingsectionalized dielectric foam 1804′ or a helix strip of dielectric foam1804″ with cores 1801′, 1801″, 1803 or 1803′). In some embodimentsguided electromagnetic waves propagating in the transmission mediums1800′, 1800″, 1800′″, and/or 1800″″ of FIG. 18K may experience lesspropagation losses than guided electromagnetic waves propagating in thetransmission mediums 1800, 1820 and 1830 of FIGS. 18A-18C. Additionally,the embodiments illustrated in FIGS. 18K-18L can be adapted to use theconnectivity embodiments illustrated in FIGS. 18I-18J.

Turning now to FIG. 18M, a block diagram illustrating an example,non-limiting embodiment of exposed tapered stubs from the bundledtransmission media 1836 for use as antennas 1855 is shown. Each antenna1855 can serve as a directional antenna for radiating wireless signalsdirected to wireless communication devices or for inducingelectromagnetic wave propagation on a surface of a transmission medium(e.g., a power line). In an embodiment, the wireless signals radiated bythe antennas 1855 can be beam steered by adapting the phase and/or othercharacteristics of the wireless signals generated by each antenna 1855.In an embodiment, the antennas 1855 can individually be placed in apie-pan antenna assembly for directing wireless signals in variousdirections.

It is further noted that the terms “core”, “cladding”, “shell”, and“foam” as utilized in the subject disclosure can comprise any types ofmaterials (or combinations of materials) that enable electromagneticwaves to remain bound to the core while propagating longitudinally alongthe core. For example, a strip of dielectric foam 1804″ describedearlier can be replaced with a strip of an ordinary dielectric material(e.g., polyethylene) for wrapping around the dielectric core 1802(referred to herein for illustration purposes only as a “wrap”). In thisconfiguration an average density of the wrap can be small as a result ofair space between sections of the wrap. Consequently, an effectivedielectric constant of the wrap can be less than the dielectric constantof the dielectric core 1802, thereby enabling guided electromagneticwaves to remain bound to the core. Accordingly, any of the embodimentsof the subject disclosure relating to materials used for core(s) andwrappings about the core(s) can be structurally adapted and/or modifiedwith other dielectric materials that achieve the result of maintainingelectromagnetic waves bound to the core(s) while they propagate alongthe core(s). Additionally, a core in whole or in part as described inany of the embodiments of the subject disclosure can comprise an opaquematerial (e.g., polyethylene). Accordingly, electromagnetic waves guidedand bound to the core will have a non-optical frequency range (e.g.,less than the lowest frequency of visible light).

FIGS. 18N, 18O, 18P, 18Q, 18R, 18S and 18T are block diagramsillustrating example, non-limiting embodiments of a waveguide device fortransmitting or receiving electromagnetic waves in accordance withvarious aspects described herein. In an embodiment, FIG. 18N illustratesa front view of a waveguide device 1865 having a plurality of slots 1863(e.g., openings or apertures) for emitting electromagnetic waves havingradiated electric fields (e-fields) 1861. In an embodiment, the radiatede-fields 1861 of pairs of symmetrically positioned slots 1863 (e.g.,north and south slots of the waveguide 1865) can be directed away fromeach other (i.e., polar opposite radial orientations about the cable1862). While the slots 1863 are shown as having a rectangular shape,other shapes such as other polygons, sector and arc shapes, ellipsoidshapes and other shapes are likewise possible. For illustration purposesonly, the term north will refer to a relative direction as shown in thefigures. All references in the subject disclosure to other directions(e.g., south, east, west, northwest, and so forth) will be relative tonorthern illustration. In an embodiment, to achieve e-fields withopposing orientations at the north and south slots 1863, for example,the north and south slots 1863 can be arranged to have a circumferentialdistance between each other that is approximately one wavelength ofelectromagnetic waves signals supplied to these slots. The waveguide1865 can have a cylindrical cavity in a center of the waveguide 1865 toenable placement of a cable 1862. In one embodiment, the cable 1862 cancomprise an insulated conductor. In another embodiment, the cable 1862can comprise an uninsulated conductor. In yet other embodiments, thecable 1862 can comprise any of the embodiments of a transmission core1852 of cable 1850 previously described.

In one embodiment, the cable 1862 can slide into the cylindrical cavityof the waveguide 1865. In another embodiment, the waveguide 1865 canutilize an assembly mechanism (not shown). The assembly mechanism (e.g.,a hinge or other suitable mechanism that provides a way to open thewaveguide 1865 at one or more locations) can be used to enable placementof the waveguide 1865 on an outer surface of the cable 1862 or otherwiseto assemble separate pieces together to form the waveguide 1865 asshown. According to these and other suitable embodiments, the waveguide1865 can be configured to wrap around the cable 1862 like a collar.

FIG. 18O illustrates a side view of an embodiment of the waveguide 1865.The waveguide 1865 can be adapted to have a hollow rectangular waveguideportion 1867 that receives electromagnetic waves 1866 generated by atransmitter circuit as previously described in the subject disclosure(e.g., see FIGS. 1 and 10A). The electromagnetic waves 1866 can bedistributed by the hollow rectangular waveguide portion 1867 into in ahollow collar 1869 of the waveguide 1865. The rectangular waveguideportion 1867 and the hollow collar 1869 can be constructed of materialssuitable for maintaining the electromagnetic waves within the hollowchambers of these assemblies (e.g., carbon fiber materials). It shouldbe noted that while the waveguide portion 1867 is shown and described ina hollow rectangular configuration, other shapes and/or other non-hollowconfigurations can be employed. In particular, the waveguide portion1867 can have a square or other polygonal cross section, an arc orsector cross section that is truncated to conform to the outer surfaceof the cable 1862, a circular or ellipsoid cross section or crosssectional shape. In addition, the waveguide portion 1867 can beconfigured as, or otherwise include, a solid dielectric material.

As previously described, the hollow collar 1869 can be configured toemit electromagnetic waves from each slot 1863 with opposite e-fields1861 at pairs of symmetrically positioned slots 1863 and 1863′. In anembodiment, the electromagnetic waves emitted by the combination ofslots 1863 and 1863′ can in turn induce electromagnetic waves 1868 onthat are bound to the cable 1862 for propagation according to afundamental wave mode without other wave modes present—such asnon-fundamental wave modes. In this configuration, the electromagneticwaves 1868 can propagate longitudinally along the cable 1862 to otherdownstream waveguide systems coupled to the cable 1862.

It should be noted that since the hollow rectangular waveguide portion1867 of FIG. 18O is closer to slot 1863 (at the northern position of thewaveguide 1865), slot 1863 can emit electromagnetic waves having astronger magnitude than electromagnetic waves emitted by slot 1863′ (atthe southern position). To reduce magnitude differences between theseslots, slot 1863′ can be made larger than slot 1863. The technique ofutilizing different slot sizes to balance signal magnitudes betweenslots can be applied to any of the embodiments of the subject disclosurerelating to FIGS. 18N, 18O, 18Q, 18S, 18U and 18V-some of which aredescribed below.

In another embodiment, FIG. 18P depicts a waveguide 1865′ that can beconfigured to utilize circuitry such as monolithic microwave integratedcircuits (MMICs) 1870 each coupled to a signal input 1872 (e.g., coaxialcable that provides a communication signal). The signal input 1872 canbe generated by a transmitter circuit as previously described in thesubject disclosure (e.g., see reference 101, 1000 of FIGS. 1 and 10A)adapted to provide electrical signals to the MMICs 1870. Each MMIC 1870can be configured to receive signal 1872 which the MMIC 1870 canmodulate and transmit with a radiating element (e.g., an antenna) toemit electromagnetic waves having radiated e-fields 1861. In oneembodiment, the MMIC's 1870 can be configured to receive the same signal1872, but transmit electromagnetic waves having e-fields 1861 ofopposing orientation. This can be accomplished by configuring one of theMMICs 1870 to transmit electromagnetic waves that are 180 degrees out ofphase with the electromagnetic waves transmitted by the other MMIC 1870.In an embodiment, the combination of the electromagnetic waves emittedby the MMICs 1870 can together induce electromagnetic waves 1868 thatare bound to the cable 1862 for propagation according to a fundamentalwave mode without other wave modes present—such as non-fundamental wavemodes. In this configuration, the electromagnetic waves 1868 canpropagate longitudinally along the cable 1862 to other downstreamwaveguide systems coupled to the cable 1862.

A tapered horn 1880 can be added to the embodiments of FIGS. 18O and 18Pto assist in the inducement of the electromagnetic waves 1868 on cable1862 as depicted in FIGS. 18Q and 18R. In an embodiment where the cable1862 is an uninsulated conductor, the electromagnetic waves induced onthe cable 1862 can have a large radial dimension (e.g., 1 meter). Toenable use of a smaller tapered horn 1880, an insulation layer 1879 canbe applied on a portion of the cable 1862 at or near the cavity asdepicted with hash lines in FIGS. 18Q and 18R. The insulation layer 1879can have a tapered end facing away from the waveguide 1865. The addedinsulation enables the electromagnetic waves 1868 initially launched bythe waveguide 1865 (or 1865′) to be tightly bound to the insulation,which in turn reduces the radial dimension of the electromagnetic fields1868 (e.g., centimeters). As the electromagnetic waves 1868 propagateaway from the waveguide 1865 (1865′) and reach the tapered end of theinsulation layer 1879, the radial dimension of the electromagnetic waves1868 begin to increase eventually achieving the radial dimension theywould have had had the electromagnetic waves 1868 been induced on theuninsulated conductor without an insulation layer. In the illustrationof FIGS. 18Q and 18R the tapered end begins at an end of the taperedhorn 1880. In other embodiments, the tapered end of the insulation layer1879 can begin before or after the end of the tapered horn 1880. Thetapered horn can be metallic or constructed of other conductive materialor constructed of a plastic or other non-conductive material that iscoated or clad with a dielectric layer or doped with a conductivematerial to provide reflective properties similar to a metallic horn.

In an embodiment, cable 1862 can comprise any of the embodiments ofcable 1850 described earlier. In this embodiment, waveguides 1865 and1865′ can be coupled to a transmission core 1852 of cable 1850 asdepicted in FIGS. 18S and 18T. The waveguides 1865 and 1865′ can induce,as previously described, electromagnetic waves 1868 on the transmissioncore 1852 for propagation entirely or partially within inner layers ofcable 1850.

It is noted that for the foregoing embodiments of FIGS. 18Q, 18R, 18Sand 18T, electromagnetic waves 1868 can be bidirectional. For example,electromagnetic waves 1868 of a different operating frequency can bereceived by slots 1863 or MMIC's 1870 of the waveguides 1865 and 1865′,respectively. Once received, the electromagnetic waves can be convertedby a receiver circuit (e.g., see reference 101, 1000 of FIGS. 1 and 10A)for generating a communication signal for processing.

Although not shown, it is further noted that the waveguides 1865 and1865′ can be adapted so that the waveguides 1865 and 1865′ can directelectromagnetic waves 1868 upstream or downstream longitudinally. Forexample, a first tapered horn 1880 coupled to a first instance of awaveguide 1865 or 1865′ can be directed westerly on cable 1862, while asecond tapered horn 1880 coupled to a second instance of a waveguide1865 or 1865′ can be directed easterly on cable 1862. The first andsecond instances of the waveguides 1865 or 1865′ can be coupled so thatin a repeater configuration, signals received by the first waveguide1865 or 1865′ can be provided to the second waveguide 1865 or 1865′ forretransmission in an easterly direction on cable 1862. The repeaterconfiguration just described can also be applied from an easterly towesterly direction on cable 1862.

The waveguide 1865 of FIGS. 18N, 18O, 18Q and 18S can also be configuredto generate electromagnetic fields having only non-fundamental orasymmetric wave modes. FIG. 18U depicts an embodiment of a waveguide1865 that can be adapted to generate electromagnetic fields having onlynon-fundamental wave modes. A median line 1890 represents a separationbetween slots where electrical currents on a backside (not shown) of afrontal plate of the waveguide 1865 change polarity. For example,electrical currents on the backside of the frontal plate correspondingto e-fields that are radially outward (i.e., point away from a centerpoint of cable 1862) can in some embodiments be associated with slotslocated outside of the median line 1890 (e.g., slots 1863A and 1863B).Electrical currents on the backside of the frontal plate correspondingto e-fields that are radially inward (i.e., point towards a center pointof cable 1862) can in some embodiments be associated with slots locatedinside of the median line 1890. The direction of the currents can dependon the operating frequency of the electromagnetic waves 1866 supplied tothe hollow rectangular waveguide portion 1867 (see FIG. 18O) among otherparameters.

For illustration purposes, assume the electromagnetic waves 1866supplied to the hollow rectangular waveguide portion 1867 have anoperating frequency whereby a circumferential distance between slots1863A and 1863B is one full wavelength of the electromagnetic waves1866. In this instance, the e-fields of the electromagnetic wavesemitted by slots 1863A and 1863B point radially outward (i.e., haveopposing orientations). When the electromagnetic waves emitted by slots1863A and 1863B are combined, the resulting electromagnetic waves oncable 1862 will propagate according to the fundamental wave mode. Incontrast, by repositioning one of the slots (e.g., slot 1863B) insidethe media line 1890 (i.e., slot 1863C), slot 1863C will generateelectromagnetic waves that have e-fields that are approximately 180degrees out of phase with the e-fields of the electromagnetic wavesgenerated by slot 1863A. Consequently, the e-field orientations of theelectromagnetic waves generated by slot pairs 1863A and 1863C will besubstantially aligned. The combination of the electromagnetic wavesemitted by slot pairs 1863A and 1863C will thus generate electromagneticwaves that are bound to the cable 1862 for propagation according to anon-fundamental wave mode.

To achieve a reconfigurable slot arrangement, waveguide 1865 can beadapted according to the embodiments depicted in FIG. 18V. Configuration(A) depicts a waveguide 1865 having a plurality of symmetricallypositioned slots. Each of the slots 1863 of configuration (A) can beselectively disabled by blocking the slot with a material (e.g., carbonfiber or metal) to prevent the emission of electromagnetic waves. Ablocked (or disabled) slot 1863 is shown in black, while an enabled (orunblocked) slot 1863 is shown in white. Although not shown, a blockingmaterial can be placed behind (or in front) of the frontal plate of thewaveguide 1865. A mechanism (not shown) can be coupled to the blockingmaterial so that the blocking material can slide in or out of aparticular slot 1863 much like closing or opening a window with a cover.The mechanism can be coupled to a linear motor controllable by circuitryof the waveguide 1865 to selectively enable or disable individual slots1863. With such a mechanism at each slot 1863, the waveguide 1865 can beconfigured to select different configurations of enabled and disabledslots 1863 as depicted in the embodiments of FIG. 18V. Other methods ortechniques for covering or opening slots (e.g., utilizing rotatabledisks behind or in front of the waveguide 1865) can be applied to theembodiments of the subject disclosure.

In one embodiment, the waveguide system 1865 can be configured to enablecertain slots 1863 outside the median line 1890 and disable certainslots 1863 inside the median line 1890 as shown in configuration (B) togenerate fundamental waves. Assume, for example, that thecircumferential distance between slots 1863 outside the median line 1890(i.e., in the northern and southern locations of the waveguide system1865) is one full wavelength. These slots will therefore have electricfields (e-fields) pointing at certain instances in time radially outwardas previously described. In contrast, the slots inside the median line1890 (i.e., in the western and eastern locations of the waveguide system1865) will have a circumferential distance of one-half a wavelengthrelative to either of the slots 1863 outside the median line. Since theslots inside the median line 1890 are half a wavelength apart, suchslots will produce electromagnetic waves having e-fields pointingradially outward. If the western and eastern slots 1863 outside themedian line 1890 had been enabled instead of the western and easternslots inside the median line 1890, then the e-fields emitted by thoseslots would have pointed radially inward, which when combined with theelectric fields of the northern and southern would producenon-fundamental wave mode propagation. Accordingly, configuration (B) asdepicted in FIG. 18V can be used to generate electromagnetic waves atthe northern and southern slots 1863 having e-fields that point radiallyoutward and electromagnetic waves at the western and eastern slots 1863with e-fields that also point radially outward, which when combinedinduce electromagnetic waves on cable 1862 having a fundamental wavemode.

In another embodiment, the waveguide system 1865 can be configured toenable a northerly, southerly, westerly and easterly slots 1863 alloutside the median line 1890, and disable all other slots 1863 as shownin configuration (C). Assuming the circumferential distance between apair of opposing slots (e.g., northerly and southerly, or westerly andeasterly) is a full wavelength apart, then configuration (C) can be usedto generate electromagnetic waves having a non-fundamental wave modewith some e-fields pointing radially outward and other fields pointingradially inward. In yet another embodiment, the waveguide system 1865can be configured to enable a northwesterly slot 1863 outside the medianline 1890, enable a southeasterly slot 1863 inside the median line 1890,and disable all other slots 1863 as shown in configuration (D). Assumingthe circumferential distance between such a pair of slots is a fullwavelength apart, then such a configuration can be used to generateelectromagnetic waves having a non-fundamental wave mode with e-fieldsaligned in a northwesterly direction.

In another embodiment, the waveguide system 1865 can be configured toproduce electromagnetic waves having a non-fundamental wave mode withe-fields aligned in a southwesterly direction. This can be accomplishedby utilizing a different arrangement than used in configuration (D).Configuration (E) can be accomplished by enabling a southwesterly slot1863 outside the median line 1890, enabling a northeasterly slot 1863inside the median line 1890, and disabling all other slots 1863 as shownin configuration (E). Assuming the circumferential distance between sucha pair of slots is a full wavelength apart, then such a configurationcan be used to generate electromagnetic waves having a non-fundamentalwave mode with e-fields aligned in a southwesterly direction.Configuration (E) thus generates a non-fundamental wave mode that isorthogonal to the non-fundamental wave mode of configuration (D).

In yet another embodiment, the waveguide system 1865 can be configuredto generate electromagnetic waves having a fundamental wave mode withe-fields that point radially inward. This can be accomplished byenabling a northerly slot 1863 inside the median line 1890, enabling asoutherly slot 1863 inside the median line 1890, enabling an easterlyslot outside the median 1890, enabling a westerly slot 1863 outside themedian 1890, and disabling all other slots 1863 as shown inconfiguration (F). Assuming the circumferential distance between thenortherly and southerly slots is a full wavelength apart, then such aconfiguration can be used to generate electromagnetic waves having afundamental wave mode with radially inward e-fields. Although the slotsselected in configurations (B) and (F) are different, the fundamentalwave modes generated by configurations (B) and (F) are the same.

It yet another embodiment, e-fields can be manipulated between slots togenerate fundamental or non-fundamental wave modes by varying theoperating frequency of the electromagnetic waves 1866 supplied to thehollow rectangular waveguide portion 1867. For example, assume in theillustration of FIG. 18U that for a particular operating frequency ofthe electromagnetic waves 1866 the circumferential distance between slot1863A and 1863B is one full wavelength of the electromagnetic waves1866. In this instance, the e-fields of electromagnetic waves emitted byslots 1863A and 1863B will point radially outward as shown, and can beused in combination to induce electromagnetic waves on cable 1862 havinga fundamental wave mode. In contrast, the e-fields of electromagneticwaves emitted by slots 1863A and 1863C will be radially aligned (i.e.,pointing northerly) as shown, and can be used in combination to induceelectromagnetic waves on cable 1862 having a non-fundamental wave mode.

Now suppose that the operating frequency of the electromagnetic waves1866 supplied to the hollow rectangular waveguide portion 1867 ischanged so that the circumferential distance between slot 1863A and1863B is one-half a wavelength of the electromagnetic waves 1866. Inthis instance, the e-fields of electromagnetic waves emitted by slots1863A and 1863B will be radially aligned (i.e., point in the samedirection). That is, the e-fields of electromagnetic waves emitted byslot 1863B will point in the same direction as the e-fields ofelectromagnetic waves emitted by slot 1863A. Such electromagnetic wavescan be used in combination to induce electromagnetic waves on cable 1862having a non-fundamental wave mode. In contrast, the e-fields ofelectromagnetic waves emitted by slots 1863A and 1863C will be radiallyoutward (i.e., away from cable 1862), and can be used in combination toinduce electromagnetic waves on cable 1862 having a fundamental wavemode.

In another embodiment, the waveguide 1865′ of FIGS. 18P, 18R and 18T canalso be configured to generate electromagnetic waves having onlynon-fundamental wave modes. This can be accomplished by adding moreMMICs 1870 as depicted in FIG. 18W. Each MMIC 1870 can be configured toreceive the same signal input 1872. However, MMICs 1870 can selectivelybe configured to emit electromagnetic waves having differing phasesusing controllable phase-shifting circuitry in each MMIC 1870. Forexample, the northerly and southerly MMICs 1870 can be configured toemit electromagnetic waves having a 180 degree phase difference, therebyaligning the e-fields either in a northerly or southerly direction. Anycombination of pairs of MMICs 1870 (e.g., westerly and easterly MMICs1870, northwesterly and southeasterly MMICs 1870, northeasterly andsouthwesterly MMICs 1870) can be configured with opposing or alignede-fields. Consequently, waveguide 1865′ can be configured to generateelectromagnetic waves with one or more non-fundamental wave modes,electromagnetic waves with one or more fundamental wave modes, or anycombinations thereof.

It is submitted that it is not necessary to select slots 1863 in pairsto generate electromagnetic waves having a non-fundamental wave mode.For example, electromagnetic waves having a non-fundamental wave modecan be generated by enabling a single slot from the plurality of slotsshown in configuration (A) of FIG. 18V and disabling all other slots.Similarly, a single MMIC 1870 of the MMICs 1870 shown in FIG. 18W can beconfigured to generate electromagnetic waves having a non-fundamentalwave mode while all other MMICs 1870 are not in use or disabled.Likewise other wave modes and wave mode combinations can be induced byenabling other non-null proper subsets of waveguide slots 1863 or theMMICs 1870.

It is further submitted that the e-field arrows shown in FIGS. 18U-18Vare illustrative only and represent a static depiction of e-fields. Inpractice, the electromagnetic waves may have oscillating e-fields, whichat one instance in time point outwardly, and at another instance in timepoint inwardly. For example, in the case of non-fundamental wave modeshaving e-fields that are aligned in one direction (e.g., northerly),such waves may at another instance in time have e-fields that point inan opposite direction (e.g., southerly). Similarly, fundamental wavemodes having e-fields that are radial may at one instance have e-fieldsthat point radially away from the cable 1862 and at another instance intime point radially towards the cable 1862. It is further noted that theembodiments of FIGS. 18U-18W can be adapted to generate electromagneticwaves with one or more non-fundamental wave modes, electromagnetic waveswith one or more fundamental wave modes (e.g., TM00 and HE11 modes), orany combinations thereof. It is further noted that such adaptions can beused in combination with any embodiments described in the subjectdisclosure. It is also noted that the embodiments of FIGS. 18U-18W canbe combined (e.g., slots used in combination with MMICs).

It is further noted that in some embodiments, the waveguide systems 1865and 1865′ of FIGS. 18N-18W may generate combinations of fundamental andnon-fundamental wave modes where one wave mode is dominant over theother. For example, in one embodiment electromagnetic waves generated bythe waveguide systems 1865 and 1865′ of FIGS. 18N-18W may have a weaksignal component that has a non-fundamental wave mode, and asubstantially strong signal component that has a fundamental wave mode.Accordingly, in this embodiment, the electromagnetic waves have asubstantially fundamental wave mode. In another embodimentelectromagnetic waves generated by the waveguide systems 1865 and 1865′of FIGS. 18N-18W may have a weak signal component that has a fundamentalwave mode, and a substantially strong signal component that has anon-fundamental wave mode. Accordingly, in this embodiment, theelectromagnetic waves have a substantially non-fundamental wave mode.Further, a non-dominant wave mode may be generated that propagates onlytrivial distances along the length of the transmission medium.

It is also noted that the waveguide systems 1865 and 1865′ of FIGS.18N-18W can be configured to generate instances of electromagnetic wavesthat have wave modes that can differ from a resulting wave mode or modesof the combined electromagnetic wave. It is further noted that each MMIC1870 of the waveguide system 1865′ of FIG. 18W can be configured togenerate an instance of electromagnetic waves having wavecharacteristics that differ from the wave characteristics of anotherinstance of electromagnetic waves generated by another MMIC 1870. OneMMIC 1870, for example, can generate an instance of an electromagneticwave having a spatial orientation and a phase, frequency, magnitude,electric field orientation, and/or magnetic field orientation thatdiffers from the spatial orientation and phase, frequency, magnitude,electric field orientation, and/or magnetic field orientation of adifferent instance of another electromagnetic wave generated by anotherMMIC 1870. The waveguide system 1865′ can thus be configured to generateinstances of electromagnetic waves having different wave and spatialcharacteristics, which when combined achieve resulting electromagneticwaves having one or more desirable wave modes.

From these illustrations, it is submitted that the waveguide systems1865 and 1865′ of FIGS. 18N-18W can be adapted to generateelectromagnetic waves with one or more selectable wave modes. In oneembodiment, for example, the waveguide systems 1865 and 1865′ can beadapted to select one or more wave modes and generate electromagneticwaves having a single wave mode or multiple wave modes selected andproduced from a process of combining instances of electromagnetic waveshaving one or more configurable wave and spatial characteristics. In anembodiment, for example, parametric information can be stored in alook-up table. Each entry in the look-up table can represent aselectable wave mode. A selectable wave mode can represent a single wavemode, or a combination of wave modes. The combination of wave modes canhave one or dominant wave modes. The parametric information can provideconfiguration information for generating instances of electromagneticwaves for producing resultant electromagnetic waves that have thedesired wave mode.

For example, once a wave mode or modes is selected, the parametricinformation obtained from the look-up table from the entry associatedwith the selected wave mode(s) can be used to identify which of one ormore MMICs 1870 to utilize, and/or their corresponding configurations toachieve electromagnetic waves having the desired wave mode(s). Theparametric information may identify the selection of the one or moreMMICs 1870 based on the spatial orientations of the MMICs 1870, whichmay be required for producing electromagnetic waves with the desiredwave mode. The parametric information can also provide information toconfigure each of the one or more MMICs 1870 with a particular phase,frequency, magnitude, electric field orientation, and/or magnetic fieldorientation which may or may not be the same for each of the selectedMMICs 1870. A look-up table with selectable wave modes and correspondingparametric information can be adapted for configuring the slottedwaveguide system 1865.

In some embodiments, a guided electromagnetic wave can be considered tohave a desired wave mode if the corresponding wave mode propagatesnon-trivial distances on a transmission medium and has a field strengththat is substantially greater in magnitude (e.g., 20 dB higher inmagnitude) than other wave modes that may or may not be desirable. Sucha desired wave mode or modes can be referred to as dominant wave mode(s)with the other wave modes being referred to as non-dominant wave modes.In a similar fashion, a guided electromagnetic wave that is said to besubstantially without the fundamental wave mode has either nofundamental wave mode or a non-dominant fundamental wave mode. A guidedelectromagnetic wave that is said to be substantially without anon-fundamental wave mode has either no non-fundamental wave mode(s) oronly non-dominant non-fundamental wave mode(s). In some embodiments, aguided electromagnetic wave that is said to have only a single wave modeor a selected wave mode may have only one corresponding dominant wavemode.

It is further noted that the embodiments of FIGS. 18U-18W can be appliedto other embodiments of the subject disclosure. For example, theembodiments of FIGS. 18U-18W can be used as alternate embodiments to theembodiments depicted in FIGS. 18N-18T or can be combined with theembodiments depicted in FIGS. 18N-18T.

Turning now to FIGS. 19A and 19B, block diagrams illustrating example,non-limiting embodiments of a dielectric antenna and corresponding gainand field intensity plots in accordance with various aspects describedherein are shown. FIG. 19A depicts a dielectric horn antenna 1901 havinga conical structure. The dielectric horn antenna 1901 is coupled to oneend 1902′ of a feedline 1902 having a feed point 1902″ at an oppositeend of the feedline 1902. The dielectric horn antenna 1901 and thefeedline 1902 (as well as other embodiments of the dielectric antennadescribed below in the subject disclosure) can be constructed ofdielectric materials such as a polyethylene material, a polyurethanematerial or other suitable dielectric material (e.g., a synthetic resin,other plastics, etc.). The dielectric horn antenna 1901 and the feedline1902 (as well as other embodiments of the dielectric antenna describedbelow in the subject disclosure) can be adapted to be substantially orentirely devoid of any conductive materials.

For example, the external surfaces 1907 of the dielectric horn antenna1901 and the feedline 1902 can be non-conductive or substantiallynon-conductive with at least 95% of the external surface area beingnon-conductive and the dielectric materials used to construct thedielectric horn antenna 1901 and the feedline 1902 can be such that thedielectric materials substantially do not contain impurities that may beconductive (e.g., such as less than 1 part per thousand) or result inimparting conductive properties. In other embodiments, however, alimited number of conductive components can be used such as a metallicconnector component used for coupling to the feed point 1902″ of thefeedline 1902 with one or more screws, rivets or other coupling elementsused to bind components to one another, and/or one or more structuralelements that do not significantly alter the radiation pattern of thedielectric antenna.

The feed point 1902″ can be adapted to couple to a core 1852 such aspreviously described by way of illustration in FIGS. 18I and 18J. In oneembodiment, the feed point 1902″ can be coupled to the core 1852utilizing a joint (not shown in FIG. 19A) such as the splicing device1860 of FIG. 18J. Other embodiments for coupling the feed point 1902″ tothe core 1852 can be used. In an embodiment, the joint can be configuredto cause the feed point 1902″ to touch an endpoint of the core 1852. Inanother embodiment, the joint can create a gap between the feed point1902″ and an end of the core 1852. In yet another embodiment, the jointcan cause the feed point 1902″ and the core 1852 to be coaxially alignedor partially misaligned. Notwithstanding any combination of theforegoing embodiments, electromagnetic waves can in whole or at least inpart propagate between the junction of the feed point 1902″ and the core1852.

The cable 1850 can be coupled to the waveguide system 1865 depicted inFIG. 18S or the waveguide system 1865′ depicted in FIG. 18T. Forillustration purposes only, reference will be made to the waveguidesystem 1865′ of FIG. 18T. It is understood, however, that the waveguidesystem 1865 of FIG. 18S or other waveguide systems can also be utilizedin accordance with the discussions that follow. The waveguide system1865′ can be configured to select a wave mode (e.g., non-fundamentalwave mode, fundamental wave mode, a hybrid wave mode, or combinationsthereof as described earlier) and transmit instances of electromagneticwaves having a non-optical operating frequency (e.g., 60 GHz). Theelectromagnetic waves can be directed to an interface of the cable 1850as shown in FIG. 18T.

The instances of electromagnetic waves generated by the waveguide system1865′ can induce a combined electromagnetic wave having the selectedwave mode that propagates from the core 1852 to the feed point 1902″.The combined electromagnetic wave can propagate partly inside the core1852 and partly on an outer surface of the core 1852. Once the combinedelectromagnetic wave has propagated through the junction between thecore 1852 and the feed point 1902″, the combined electromagnetic wavecan continue to propagate partly inside the feedline 1902 and partly onan outer surface of the feedline 1902. In some embodiments, the portionof the combined electromagnetic wave that propagates on the outersurface of the core 1852 and the feedline 1902 is small. In theseembodiments, the combined electromagnetic wave can be said to be guidedby and tightly coupled to the core 1852 and the feedline 1902 whilepropagating longitudinally towards the dielectric antenna 1901.

When the combined electromagnetic wave reaches a proximal portion of thedielectric antenna 1901 (at a junction 1902′ between the feedline 1902and the dielectric antenna 1901), the combined electromagnetic waveenters the proximal portion of the dielectric antenna 1901 andpropagates longitudinally along an axis of the dielectric antenna 1901(shown as a hashed line). By the time the combined electromagnetic wavereaches the aperture 1903, the combined electromagnetic wave has anintensity pattern similar to the one shown by the side view and frontview depicted in FIG. 19B. The electric field intensity pattern of FIG.19B shows that the electric fields of the combined electromagnetic wavesare strongest in a center region of the aperture 1903 (see the examplegiven of “61 dBV/m and the label “Higher field intensity”) and weaker inthe outer regions (see the example given of “29 dBV/m and the label“Lower field intensity”). In an embodiment, where the wave mode of theelectromagnetic waves propagating in the dielectric antenna 1901 is ahybrid wave mode (e.g., HE11), the leakage of the electromagnetic wavesat the external surfaces 1907 is reduced or in some instanceseliminated. It is further noted that while the dielectric antenna 1901is constructed of a solid dielectric material having no physicalopening, the front or operating face of the dielectric antenna 1901 fromwhich free space wireless signals (see, e.g., “RF out” shown in FIG.19A) are radiated or received will be referred to as the aperture 1903of the dielectric antenna 1901 even though in some prior art systems theterm aperture may be used to describe an opening of an antenna thatradiates or receives free space wireless signals. In the example shownin FIG. 19A, certain dimensions can be 3 mm, 6 cm and 3 cm as indicated.Methods for launching a hybrid wave mode on cable 1850 is discussedbelow.

In an embodiment, the far-field antenna gain pattern depicted in FIG.19B can be widened by decreasing the operating frequency of the combinedelectromagnetic wave from a nominal frequency. Similarly, the gainpattern can be narrowed by increasing the operating frequency of thecombined electromagnetic wave from the nominal frequency. Accordingly, awidth of a beam of wireless signals emitted by the aperture 1903 can becontrolled by configuring the waveguide system 1865′ to increase ordecrease the operating frequency of the combined electromagnetic wave.

The dielectric antenna 1901 of FIG. 19A can also be used for receivingwireless signals, such as free space wireless signals transmitted byeither a similar antenna or conventional antenna design. Wirelesssignals received by the dielectric antenna 1901 at the aperture 1903induce electromagnetic waves in the dielectric antenna 1901 thatpropagate towards the feedline 1902. The electromagnetic waves continueto propagate from the feedline 1902 to the junction between the feedpoint 1902″ and an endpoint of the core 1852, and are thereby deliveredto the waveguide system 1865′ coupled to the cable 1850 as shown in FIG.18T. In this configuration, the waveguide system 1865′ can performbidirectional communications utilizing the dielectric antenna 1901. Itis further noted that in some embodiments the core 1852 of the cable1850 (shown with dashed lines) can be configured to be collinear withthe feed point 1902″ to avoid a bend shown in FIG. 19A. In someembodiments, a collinear configuration can reduce an alteration in thepropagation of the electromagnetic due to the bend in cable 1850.

Turning now to FIGS. 19C and 19D, block diagrams illustrating example,non-limiting embodiments of a dielectric antenna 1901 coupled to orintegrally constructed with a lens 1912 (as shown in FIG. 19C) andcorresponding gain and field intensity plots in accordance with variousaspects described herein are shown in FIG. 19D. In one embodiment, thelens 1912 can comprise a dielectric material having a first dielectricconstant that is substantially similar or equal to a second dielectricconstant of the dielectric antenna 1901. In other embodiments, the lens1912 can comprise a dielectric material having a first dielectricconstant that differs from a second dielectric constant of thedielectric antenna 1901. In either of these embodiments, the shape ofthe lens 1912 can be chosen or formed so as to equalize the delays ofthe various electromagnetic waves propagating at different points in thedielectric antenna 1901. In one embodiment, the lens 1912 can be anintegral part of the dielectric antenna 1901 as depicted in the topdiagram of FIG. 19C and in particular, the lens and dielectric antenna1901 can be molded, machined or otherwise formed from a single piece ofdielectric material. Alternatively, the lens 1912 can be an assemblycomponent of the dielectric antenna 1901 as depicted in the bottomdiagram of FIG. 19C, which can be attached by way of an adhesivematerial, brackets on the outer edges, or other suitable attachmenttechniques. The lens 1912 can have a convex structure as shown in FIG.19C which is adapted to adjust a propagation of electromagnetic waves inthe dielectric antenna 1901. While a round lens and conical dielectricantenna configuration is shown, other shapes include pyramidal shapes,elliptical shapes and other geometric shapes can likewise beimplemented.

In particular, the curvature of the lens 1912 can be chosen in mannerthat reduces phase differences between near-field wireless signalsgenerated by the aperture 1903 of the dielectric antenna 1901 (as shownin FIG. 19C). The lens 1912 (as shown in FIG. 19C) accomplishes this byapplying location-dependent delays to propagating electromagnetic waves.Because of the curvature of the lens 1912, the delays differ dependingon where the electromagnetic waves emanate from at the aperture 1903.For example, electromagnetic waves propagating by way of a center axis1905 (i.e., the top diagram in FIG. 19C) of the dielectric antenna 1901will experience more delay through the lens 1901 than electromagneticwaves propagating radially away from the center axis 1905.Electromagnetic waves propagating towards, for example, the outer edgesof the aperture 1903 will experience minimal or no delay through thelens. Propagation delay increases as the electromagnetic waves get closeto the center axis 1905. Accordingly, a curvature of the lens 1912 canbe configured so that near-field wireless signals have substantiallysimilar phases. By reducing differences between phases of the near-fieldwireless signals, a width of far-field signals generated by thedielectric antenna 1901 is reduced, which in turn increases theintensity of the far-field wireless signals within the width of the mainlobe as shown by the far-field intensity plot shown in FIG. 19D,producing a relatively narrow beam pattern with high gain.

Turning now to FIGS. 19E and 19F, block diagrams illustrating example,non-limiting embodiments of a dielectric antenna 1901 coupled to a lens1912 with ridges (or steps) 1914 (as shown in FIG. 19E) andcorresponding gain and field intensity plots in accordance with variousaspects described herein are shown in FIG. 19F. In these illustration,the lens 1912 can comprise concentric ridges 1914 shown in the side andperspective views of FIG. 19E. Each ridge 1914 can comprise a riser 1916and a tread 1918 (as shown in the top diagram in FIG. 19E). The size ofthe tread 1918 changes depending on the curvature of the aperture 1903(as shown in FIG. 19E). For example, the tread 1918 at the center of theaperture 1903 can be greater than the tread at the outer edges of theaperture 1903. To reduce reflections of electromagnetic waves that reachthe aperture 1903, each riser 1916 can be configured to have a depthrepresentative of a select wavelength factor. For example, a riser 1916can be configured to have a depth of one-quarter a wavelength of theelectromagnetic waves propagating in the dielectric antenna 1901. Such aconfiguration causes the electromagnetic wave reflected from one riser1916 to have a phase difference of 180 degrees relative to theelectromagnetic wave reflected from an adjacent riser 1916.Consequently, the out of phase electromagnetic waves reflected from theadjacent risers 1916 substantially cancel, thereby reducing reflectionand distortion caused thereby. While a particular riser/treadconfiguration is shown, other configurations with a differing number ofrisers, differing riser shapes, etc. can likewise be implemented. Insome embodiments, the lens 1912 with concentric ridges depicted in FIG.19E may experience less electromagnetic wave reflections than the lens1912 having the smooth convex surface depicted in FIG. 19C. FIG. 19Fdepicts the resulting far-field gain plot of the dielectric antenna 1901of FIG. 19E.

Turning now to FIG. 19G, a block diagram illustrating an example,non-limiting embodiment of a dielectric antenna 1901 having anelliptical structure in accordance with various aspects described hereinis shown. FIG. 19G depicts a side view, top view, and front view of thedielectric antenna 1901. The elliptical shape is achieved by reducing aheight of the dielectric antenna 1901 as shown by reference 1922 and byelongating the dielectric antenna 1901 as shown by reference 1924. Theresulting elliptical shape 1926 is shown in the front view depicted byFIG. 19G. The elliptical shape can be formed, via machining, with a moldtool or other suitable construction technique.

Turning now to FIG. 19H, a block diagram illustrating an example,non-limiting embodiment of near-field signals 1928 and far-field signals1930 emitted by the dielectric antenna 1901 of FIG. 19G in accordancewith various aspects described herein is shown. The cross section of thenear-field beam pattern 1928 mimics the elliptical shape of the aperture1903 of the dielectric antenna 1901 (see respective example axes θ_(V)and θ_(H)). The cross section of the far-field beam pattern 1930 (seerespective example axes θ_(V) and θ_(H)) have a rotational offset(approximately 90 degrees) that results from the elliptical shape of thenear-field signals 1928. The offset can be determined by applying aFourier Transform to the near-field signals 1928. While the crosssection of the near-field beam pattern 1928 and the cross section of thefar-field beam pattern 1930 are shown as nearly the same size in orderto demonstrate the rotational effect, the actual size of the far-fieldbeam pattern 1930 may increase with the distance from the dielectricantenna 1901.

The elongated shape of the far-field signals 1930 and its orientationcan prove useful when aligning a dielectric antenna 1901 in relation toa remotely located receiver configured to receive the far-field signals1930. The receiver can comprise one or more dielectric antennas coupledto a waveguide system such as described by the subject disclosure. Theelongated far-field signals 1930 can increase the likelihood that theremotely located receiver will detect the far-field signals 1930. Inaddition, the elongated far-field signals 1930 can be useful insituations where a dielectric antenna 1901 coupled to a gimbal assemblysuch as shown in FIG. 19M, or other actuated antenna mount including butnot limited to the actuated gimbal mount described in the co-pendingapplication entitled, COMMUNICATION DEVICE AND ANTENNA ASSEMBLY WITHACTUATED GIMBAL MOUNT, and U.S. patent application Ser. No. 14/873,241,filed on Oct. 2, 2015 (now U.S. Pat. No. 9,882,277, issued on Jan. 30,2018) the contents of which are incorporated herein by reference for anyand all purposes. In particular, the elongated far-field signals 1930can be useful in situations where such as gimbal mount only has twodegrees of freedom for aligning the dielectric antenna 1901 in thedirection of the receiver (e.g., yaw and pitch is adjustable but roll isfixed).

Although not shown, it will be appreciated that the dielectric antenna1901 of FIGS. 19G and 19H can have an integrated or attachable lens 1912such as shown in FIGS. 19C and 19E to increase an intensity of thefar-fields signals 1930 by reducing phase differences in the near-fieldsignals.

Turning now to FIG. 19I, block diagrams of example, non-limitingembodiments of a dielectric antenna 1901 for adjusting far-fieldwireless signals in accordance with various aspects described herein areshown. In some embodiments, a width of far-field wireless signalsgenerated by the dielectric antenna 1901 can be said to be inverselyproportional to a number of wavelengths of the electromagnetic wavespropagating in the dielectric antenna 1901 that can fit in a surfacearea of the aperture 1903 of the dielectric antenna 1901. Hence, as thewavelengths of the electromagnetic waves increases, the width of thefar-field wireless signals increases (and its intensity decreases)proportionately. Put another way, when the frequency of theelectromagnetic waves decreases, the width of the far-field wirelesssignals increases proportionately. Accordingly, to enhance a process ofaligning a dielectric antenna 1901 using, for example, the gimbalassembly shown in FIG. 19M or other actuated antenna mount, in adirection of a receiver, the frequency of the electromagnetic wavessupplied to the dielectric antenna 1901 by way of the feedline 1902 canbe decreased so that the far-field wireless signals are sufficientlywide to increase a likelihood that the receiver will detect a portion ofthe far-field wireless signals.

In some embodiments, the receiver can be configured to performmeasurements on the far-field wireless signals. From these measurementsthe receiver can direct a waveguide system coupled to the dielectricantenna 1901 generating the far-field wireless signals. The receiver canprovide instructions to the waveguide system by way of anomnidirectional wireless signal or a tethered interface therebetween.The instructions provided by the receiver can result in the waveguidesystem controlling actuators in the gimbal assembly coupled to thedielectric antenna 1901 to adjust a direction of the dielectric antenna1901 to improve its alignment to the receiver. As the quality of thefar-field wireless signals improves, the receiver can also direct thewaveguide system to increase a frequency of the electromagnetic waves,which in turn reduces a width of the far-field wireless signals andcorrespondingly increases its intensity.

In an alternative embodiment, absorption sheets 1932 constructed fromcarbon or conductive materials and/or other absorbers can be embedded inthe dielectric antenna 1901 as depicted by the perspective and frontviews shown in FIG. 19I. When the electric fields of the electromagneticwaves are parallel with the absorption sheets 1932, the electromagneticwaves are absorbed. A clearance region 1934 where absorption sheets 1932are not present will, however, allow the electromagnetic waves topropagate to the aperture 1903 and thereby emit near-field wirelesssignals having approximately the width of the clearance region 1934. Byreducing the number of wavelengths to a surface area of the clearanceregion 1932, the width of the near-field wireless signals is decreases,while the width of the far-field wireless signals is increased. Thisproperty can be useful during the alignment process previouslydescribed.

For example, at the onset of an alignment process, the polarity of theelectric fields emitted by the electromagnetic waves can be configuredto be parallel with the absorption sheets 1932. As the remotely locatedreceiver instructs a waveguide system coupled to the dielectric antenna1901 to direct the dielectric antenna 1901 using the actuators of agimbal assembly or other actuated mount, it can also instruct thewaveguide system to incrementally adjust the alignment of the electricfields of the electromagnetic waves relative to the absorption sheets1932 as signal measurements performed by the receiver improve. As thealignment improves, eventually waveguide system adjusts the electricfields so that they are orthogonal to the absorption sheets 1932. Atthis point, the electromagnetic waves near the absorption sheets 1932will no longer be absorbed, and all or substantially all electromagneticwaves will propagate to the aperture 1903. Since the near-field wirelesssignals now cover all or substantially all of the aperture 1903, thefar-field signals will have a narrower width and higher intensity asthey are directed to the receiver.

It will be appreciated that the receiver configured to receive thefar-field wireless signals (as described above) can also be configuredto utilize a transmitter that can transmit wireless signals directed tothe dielectric antenna 1901 utilized by the waveguide system. Forillustration purposes, such a receiver will be referred to as a remotesystem that can receive far-field wireless signals and transmit wirelesssignals directed to the waveguide system. In this embodiment, thewaveguide system can be configured to analyze the wireless signals itreceives by way of the dielectric antenna 1901 and determine whether aquality of the wireless signals generated by the remote system justifiesfurther adjustments to the far-field signal pattern to improve receptionof the far-field wireless signals by the remote system, and/or whetherfurther orientation alignment of the dielectric antenna by way of thegimbal (see FIG. 19M) or other actuated mount is needed. As the qualityof a reception of the wireless signals by the waveguide system improves,the waveguide system can increase the operating frequency of theelectromagnetic waves, which in turn reduces a width of the far-fieldwireless signals and correspondingly increases its intensity. In othermodes of operation, the gimbal or other actuated mount can beperiodically adjusted to maintain an optimal alignment.

The foregoing embodiments of FIG. 19I can also be combined. For example,the waveguide system can perform adjustments to the far-field signalpattern and/or antenna orientation adjustments based on a combination ofan analysis of wireless signals generated by the remote system andmessages or instructions provided by the remote system that indicate aquality of the far-field signals received by the remote system.

Turning now to FIG. 19J, block diagrams of example, non-limitingembodiments of a collar such as a flange 1942 that can be coupled to adielectric antenna 1901 in accordance with various aspects describedherein is shown. The flange can be constructed with metal (e.g.,aluminum) dielectric material (e.g., polyethylene and/or foam), or othersuitable materials. The flange 1942 can be utilized to align the feedpoint 1902″ (and in some embodiments also the feedline 1902) with awaveguide system 1948 (e.g., a circular or rectangular waveguide) asshown in FIG. 19K. To accomplish this, the flange 1942 can comprise acenter hole 1946 for engaging with the feed point 1902″. In oneembodiment, the hole 1946 can be threaded and the feedline 1902 can havea smooth surface. In this embodiment, the flange 1946 can engage thefeed point 1902″ (constructed of a dielectric material such aspolyethylene) by inserting a portion of the feed point 1902″ into thehole 1946 and rotating the flange 1946 to act as a die to formcomplementary threads on the soft outer surface of the feedline 1902.

Once the feedline 1902 has been threaded by or into the flange 1946, thefeed point 1902″ and a portion of the feedline 1902 extending from theflange 1946 can be shortened or lengthened by rotating the flange 1942(or antenna 1901) accordingly. In other embodiments the feedline 1902can be pre-threaded with mating threads for improving the ease ofengaging feedline 1902 with the flange 1942. In yet other embodiments,the feedline 1902 can have a smooth surface and the hole 1946 of theflange 1942 can be non-threaded. In this embodiment, the hole 1946 canhave a diameter that is similar to a diameter of the feedline 1902 suchas to cause the engagement of the feedline 1902 to be held in place byfrictional forces.

For alignment purposes, the flange 1942 the can further include threadedholes 1944 accompanied by two or more alignment holes 1947, which can beused to align to complementary alignment pins 1949 of the waveguidesystem 1948, which in turn assist in aligning holes 1944′ of thewaveguide system 1948 to the threaded holes 1944 of the flange 1942 (seeFIGS. 19K and 19L1). Once the flange 1942 has been aligned to thewaveguide system 1948, the flange 1942 and waveguide system 1948 can besecured to each other with threaded screws 1950 resulting in a completedassembly depicted in FIG. 19L1. In a threaded design of the hole 1946 ofthe flange 1942, the feed point 1902″ of the feedline 1902 can beadjusted inwards or outwards in relation to a port 1945 of the waveguidesystem 1948 from which electromagnetic waves are exchanged. Theadjustment enables the gap 1943 between the feed point 1902″ and theport 1945 to be increased or decreased. The adjustment can be used fortuning a coupling interface between the waveguide system 1948 and thefeed point 1902″ of the feedline 1902. In other embodiments, the feedpoint 1902″ can be adjusted so that it protrudes into port 1945 of thewaveguide system 1948. The extent to which the feed point 1902″protrudes into port 1945 can be adjusted inwards or outwards by rotatingthe feedline 1902 (or the flange 1942) about the threaded design of thehole 1946 of the flange 1942.

FIG. 19L1 also shows how the flange 1942 can be used to align thefeedline 1902 with coaxially aligned dielectric foam sections 1951 heldby a tubular outer jacket 1952, which is similar to the transmissionmedium 1800′ illustrated in FIG. 18K. To complete the assembly process,the flange 1942 can be coupled to a waveguide system 1948 as depicted inFIG. 19L1.

It will be appreciated that feed point 1902″ of the feedline 1902 can beconfigured to reduce reflections of the electromagnetic waves receivedfrom the waveguide system 1948. For example, the feed point 1902″ can beconfigured with a conical structure 1902′″ as shown in FIG. 19L1. Thegradual slope of the conical structure 1902′″ can enable electromagneticwaves to propagate from the waveguide system 1948 to the feedline 1902with minimal or no reflections. It will be appreciated that otherstructures that can facilitate a reduction in reflections ofelectromagnetic waves can also be used. For example, the feed point1902″ can have a slanted tapered structure much like the tapered end ofthe stub coupler 904 shown in FIG. 9A. The slanted tapered structureprovides a gradual or smooth transition for an electromagnetic wave topropagate from the waveguide system 1948 to the feedline 1902, therebyreducing reflections of the electromagnetic wave. Other structuralconfigurations of the feed point 1902″ of the feedline 1902 can also beused to reduce reflections such as, for example, a conical structurewith a rounded endpoint, a more elongated tapered structure, a taperedstructure with a greater or lesser slope, a more elongated conicalstructure, a conical structure with a greater or lesser slope, and soon. It will be further appreciated that the feed point 1902″ andfeedline 1902 can have other structural shapes such as, for example, anon-cylindrical structure (e.g., a square, oval, hexagonal, orpentagonal feed point 1902″ and/or feedline 1902).

FIGS. 19L2 and 19L3 are block diagrams illustrating example,non-limiting embodiments of connector configurations that can be usedwith a transmission medium and/or antenna in accordance with variousaspects described herein. FIG. 19L2 illustrates a transmission core 1852of a cable 1850 having a conical endpoint 1961 that can be mated toanother transmission core 1852 of another cable 1850 having a conicalcavity 1961′. The mating structure of the cables 1850 enables theelectromagnetic waves to propagate between transmission cores 1852 withno reflections or a reduction of reflections of the electromagneticwaves. FIG. 19L3 depicts a splicing device 1860 having conical cavities1961′ at two ends that can mate with conical endpoints 1961 ofcorresponding transmission cores 1852 of cables 1850. Such a matingstructure can also eliminate or reduce reflections of electromagneticwaves propagating from one cable to another. It will be appreciated thatthe cavity 1961′ and endpoints 1961 of the cables 1850 and/or splicingdevice 1860 can have different structural configuration (such asdescribed above for the feed point 1902″ and feedline 1902) to achievesimilar results. It will be further appreciated that the feed point1902″ of the feedline 1902 can be mated to the endpoint 1961 of a cable1850 using the techniques shown in FIG. 19L2 or 19L3.

FIG. 19L4 illustrates a flow diagram of, an example, non-limitingembodiment of a method 1962 for transmitting signals in accordance withvarious aspects described herein. Method 1962 can begin with step 1963where each transmitting device of one or more hollow waveguides receivescommunication signals. The communication signals can be a voice signal,a video streaming signal, internet traffic signals, other communicationsignals, or any combinations thereof. The communication signals can bebaseband signals or signals that have been modulated according to aselect signaling protocol (e.g., LTE) operating at a particularfrequency band (e.g., 1.9 GHz LTE signal). At step 1964, eachtransmitting device can be configured to generate, according to thecommunication signals, a plurality of electromagnetic waves having oneor more corresponding wave modes that couples, via a feed point 1902″,onto a feedline 1902 of one or more antennas 1901 using any one (orcombinations of) the coupling techniques illustrated in FIGS. 19L1-L3.The one or more antennas 1901 in turn convert the electromagnetic wavesto wireless signals that are generated from an aperture of each antenna1901. Each transmitting device can be configured to select at least oneMIMO technique to generate the electromagnetic wave transmissions.Additionally, each transmitting device can be configured to frequencyshift the communication signals to a suitable frequency band withoutmodifying or re-modulating the signaling protocol of the communicationsignals. Each transmitting device can also be configured to transmit areference signal with the electromagnetic waves to enable one or morereceiving devices to mitigate signal distortion (e.g., phase error). Thereference signal can also be modulated to include control channelinstructions directed to the one or more receiving devices. Thereference signal can also be accompanied by a clock signal for providingthe one or more receiving devices synchronization data.

FIG. 19L5 illustrates a flow diagram of, an example, non-limitingembodiment of a method 1966 for receiving signals in accordance withvarious aspects described herein. Method 1966 can begin with step 1967where each receiving device of one or more hollow waveguides isconfigured to receive and process one or more electromagnetic wavesgenerated by one or more corresponding antennas 1901 receiving wirelesssignals. The one or more antennas 1901 can be coupled to the hollowwaveguides using any one (or combinations) of the techniques illustratedin FIGS. 19L1-L3. Each receiving device can use at least one MIMOtechnique to process the plurality of electromagnetic waves and therebyextract at step 1968 the communication signals conveyed by the wirelesssignals received by the one or more antennas 1901. The extractionprocess can include signal amplification, frequency-shifting, andfiltering, among other things. In addition, each receiving device canuse a reference signal included in the one or more electromagnetic wavesto mitigate signal distortion, can use a clock signal (if present) forsynchronization, and can obtain control channel instructions if thereference signal is modulated with such instructions. The controlchannel instructions can be used, for example, to determine whichcommunication signals are to be distributed wirelessly to localcommunication devices (e.g., mobile phones or other communicationdevices), and which communication signals are to be retransmitted aswireless signals to one or more other receiving devices using thetechniques described above for the transmitting device(s).

It will be appreciated that the foregoing embodiments of the methods ofFIGS. 19L4-19L5 can be adapted to connect splices of a transmissionmedium as shown in FIGS. 19L2-19L3 for surface wave transmissions, or tojoin a transmission core 1852 of a cable 1850 to a feed point 1902″ of afeedline 1902 of an antenna 1901.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIGS. 19L4and 19L5, respectively, it is to be understood and appreciated that theclaimed subject matter is not limited by the order of the blocks, assome blocks may occur in different orders and/or concurrently with otherblocks from what is depicted and described herein. Moreover, not allillustrated blocks may be required to implement the methods describedherein.

Turning now to FIG. 19N, a block diagram of an example, non-limitingembodiment of a dielectric antenna 1901′ in accordance with variousaspects described herein is shown. FIG. 19N depicts an array ofpyramidal-shaped dielectric horn antennas 1901′, each having acorresponding aperture 1903′. Each antenna of the array ofpyramidal-shaped dielectric horn antennas 1901′ can have a feedline 1902with a corresponding feed point 1902″ that couples to each correspondingcore 1852 of a plurality of cables 1850. Each cable 1850 can be coupledto a different (or a same) waveguide system 1865′ such as shown in FIG.18T. The array of pyramidal-shaped dielectric horn antennas 1901′ can beused to transmit wireless signals having a plurality of spatialorientations. An array of pyramidal-shaped dielectric horn antennas1901′ covering 360 degrees can enable a one or more waveguide systems1865′ coupled to the antennas to perform omnidirectional communicationswith other communication devices or antennas of similar type.

The bidirectional propagation properties of electromagnetic wavespreviously described for the dielectric antenna 1901 of FIG. 19A arealso applicable for electromagnetic waves propagating from the core 1852to the feed point 1902″ guided by the feedline 1902 to the aperture1903′ of the pyramidal-shaped dielectric horn antennas 1901′, and in thereverse direction. Similarly, the array of pyramidal-shaped dielectrichorn antennas 1901′ can be substantially or entirely devoid ofconductive external surfaces and internal conductive materials asdiscussed above. For example, in some embodiments, the array ofpyramidal-shaped dielectric horn antennas 1901′ and their correspondingfeed points 1902′ can be constructed of dielectric-only materials suchas polyethylene or polyurethane materials or with only trivial amountsof conductive material that does not significantly alter the radiationpattern of the antenna.

It is further noted that each antenna of the array of pyramidal-shapeddielectric horn antennas 1901′ can have similar gain and electric fieldintensity maps as shown for the dielectric antenna 1901 in FIG. 19B.Each antenna of the array of pyramidal-shaped dielectric horn antennas1901′ can also be used for receiving wireless signals as previouslydescribed for the dielectric antenna 1901 of FIG. 19A. In someembodiments, a single instance of a pyramidal-shaped dielectric hornantenna can be used. Similarly, multiple instances of the dielectricantenna 1901 of FIG. 19A can be used in an array configuration similarto the one shown in FIG. 19N.

Turning now to FIG. 19O, block diagrams of example, non-limitingembodiments of an array 1976 of dielectric antennas 1901 configurablefor steering wireless signals in accordance with various aspectsdescribed herein is shown. The array 1976 of dielectric antennas 1901can be conical shaped antennas 1901 or pyramidal-shaped dielectricantennas 1901′. To perform beam steering, a waveguide system coupled tothe array 1976 of dielectric antennas 1901 can be adapted to utilize acircuit 1972 comprising amplifiers 1973 and phase shifters 1974 (seerespective “a” symbols), each pair coupled to one of the dielectricantennas 1901 in the array 1976. The waveguide system can steerfar-field wireless signals from left to right (west to east) byincrementally increasing a phase delay of signals supplied to thedielectric antennas 1901.

For example, the waveguide system can provide a first signal to thedielectric antennas of column 1 (“C1”) having no phase delay. Thewaveguide system can further provide a second signal to column 2 (“C2”),the second signal comprising the first signal having a first phasedelay. The waveguide system can further provide a third signal to thedielectric antennas of column 3 (“C3”), the third signal comprising thesecond signal having a second phase delay. Lastly, the waveguide systemcan provide a fourth signal to the dielectric antennas of column 4(“C4”), the fourth signal comprising the third signal having a thirdphase delay. These phase shifted signals will cause far-field wirelesssignals generated by the array to shift from left to right. Similarly,far-field signals can be steered from right to left (east to west) (“C4”to C1), north to south (“R1” to “R4”), south to north (“R4” to “R1”),and southwest to northeast (“C1-R4” to “C4-R1”).

Utilizing similar techniques beam steering can also be performed inother directions such as southwest to northeast by configuring thewaveguide system to incrementally increase the phase of signalstransmitted by the following sequence of antennas: “C1-R4”,“C1-R3/C2-R4”, “C1-R2/C2-R3/C3-R4”, “C1-R1/C2-R2/C3-R3/C4-R4”,“C2-R1/C3-R2/C4-R3”, “C3-R1/C4-R2”, “C4-R1”. In a similar way, beamsteering can be performed northeast to southwest, northwest tosoutheast, southeast to northwest, as well in other directions inthree-dimensional space. Beam steering can be used, among other things,for aligning the array 1976 of dielectric antennas 1901 with a remotereceiver and/or for directivity of signals to mobile communicationdevices. In some embodiments, a phased array 1976 of dielectric antennas1976 can also be used to circumvent the use of the gimbal assembly ofFIG. 19M or other actuated mount. While the foregoing has described beamsteering controlled by phase delays, gain and phase adjustment canlikewise be applied to the dielectric antennas 1901 of the phased array1976 in a similar fashion to provide additional control and versatilityin the formation of a desired beam pattern.

Turning now to FIGS. 20A and 20B, block diagrams illustrating example,non-limiting embodiments of the cable 1850 of FIG. 18A used for inducingguided electromagnetic waves on power lines supported by utility poles.In one embodiment, as depicted in FIG. 20A, a cable 1850 can be coupledat one end to a microwave apparatus that launches guided electromagneticwaves within one or more inner layers of cable 1850 utilizing, forexample, the hollow waveguide 1808 shown in FIGS. 18A-18C. The microwaveapparatus can utilize a microwave transceiver such as shown in FIG. 10Afor transmitting or receiving signals from cable 1850. The guidedelectromagnetic waves induced in the one or more inner layers of cable1850 can propagate to an exposed stub of the cable 1850 located inside ahorn antenna (shown as a dotted line in FIG. 20A) for radiating theelectromagnetic waves via the horn antenna. The radiated signals fromthe horn antenna in turn can induce guided electromagnetic waves thatpropagate longitudinally on power line such as a medium voltage (MV)power line. In one embodiment, the microwave apparatus can receive ACpower from a low voltage (e.g., 220V) power line. Alternatively, thehorn antenna can be replaced with a stub antenna as shown in FIG. 20B toinduce guided electromagnetic waves that propagate longitudinally on apower line such as the MV power line or to transmit wireless signals toother antenna system(s).

In an alternative embodiment, the hollow horn antenna shown in FIG. 20Acan be replaced with a solid dielectric antenna such as the dielectricantenna 1901 of FIG. 19A, or the pyramidal-shaped horn antenna 1901′ ofFIG. 19N. In this embodiment the horn antenna can radiate wirelesssignals directed to another horn antenna such as the bidirectional hornantennas 2040 shown in FIG. 20C. In this embodiment, each horn antenna2040 can transmit wireless signals to another horn antenna 2040 orreceive wireless signals from the other horn antenna 2040 as shown inFIG. 20C. Such an arrangement can be used for performing bidirectionalwireless communications between antennas. Although not shown, the hornantennas 2040 can be configured with an electromechanical device tosteer a direction of the horn antennas 2040.

In alternate embodiments, first and second cables 1850A′ and 1850B′ canbe coupled to the microwave apparatus and to a transformer 2052,respectively, as shown in FIGS. 20A and 20B. The first and second cables1850A′ and 1850B′ can be represented by, for example, cable 1820 orcable 1830 of FIGS. 18B and 18C, respectively, each having a conductivecore. A first end of the conductive core of the first cable 1850A′ canbe coupled to the microwave apparatus for propagating guidedelectromagnetic waves launched therein. A second end of the conductivecore of the first cable 1850A′ can be coupled to a first end of aconductive coil of the transformer 2052 for receiving the guidedelectromagnetic waves propagating in the first cable 1850A′ and forsupplying signals associated therewith to a first end of a second cable1850B′ by way of a second end of the conductive coil of the transformer2052. A second end of the second cable 1850B′ can be coupled to the hornantenna of FIG. 20A or can be exposed as a stub antenna of FIG. 20B forinducing guided electromagnetic waves that propagate longitudinally onthe MV power line.

In an embodiment where cable 1850, 1850A′ and 1850B′ each comprisemultiple instances of transmission mediums 1800, 1820, and/or 1830, apoly-rod structure of antennas 1855 can be formed such as shown in FIG.18K. Each antenna 1855 can be coupled, for example, to a horn antennaassembly as shown in FIG. 20A or a pie-pan antenna assembly (not shown)for radiating multiple wireless signals. Alternatively, the antennas1855 can be used as stub antennas in FIG. 20B. The microwave apparatusof FIGS. 20A-20B can be configured to adjust the guided electromagneticwaves to beam steer the wireless signals emitted by the antennas 1855.One or more of the antennas 1855 can also be used for inducing guidedelectromagnetic waves on a power line.

Turning now to FIG. 20C, a block diagram of an example, non-limitingembodiment of a communication network 2000 in accordance with variousaspects described herein is shown. In one embodiment, for example, thewaveguide system 1602 of FIG. 16A can be incorporated into networkinterface devices (NIDs) such as NIDs 2010 and 2020 of FIG. 20C. A NIDhaving the functionality of waveguide system 1602 can be used to enhancetransmission capabilities between customer premises 2002 (enterprise orresidential) and a pedestal 2004 (sometimes referred to as a servicearea interface or SAI).

In one embodiment, a central office 2030 can supply one or more fibercables 2026 to the pedestal 2004. The fiber cables 2026 can providehigh-speed full-duplex data services (e.g., 1-100 Gbps or higher) tomini-DSLAMs 2024 located in the pedestal 2004. The data services can beused for transport of voice, internet traffic, media content services(e.g., streaming video services, broadcast TV), and so on. In prior artsystems, mini-DSLAMs 2024 typically connect to twisted pair phone lines(e.g., twisted pairs included in category 5e or Cat. 5e unshieldedtwisted-pair (UTP) cables that include an unshielded bundle of twistedpair cables, such as 24 gauge insulated solid wires, surrounded by anouter insulating sheath), which in turn connect to the customer premises2002 directly. In such systems, DSL data rates taper off at 100 Mbps orless due in part to the length of legacy twisted pair cables to thecustomer premises 2002 among other factors.

The embodiments of FIG. 20C, however, are distinct from prior art DSLsystems. In the illustration of FIG. 20C, a mini-DSLAM 2024, forexample, can be configured to connect to NID 2020 via cable 1850 (whichcan represent in whole or in part any of the cable embodiments describedin relation to FIGS. 18A-18D and 18F-18L singly or in combination).Utilizing cable 1850 between customer premises 2002 and a pedestal 2004,enables NIDs 2010 and 2020 to transmit and receive guide electromagneticwaves for uplink and downlink communications. Based on embodimentspreviously described, cable 1850 can be exposed to rain, or can beburied without adversely affecting electromagnetic wave propagationeither in a downlink path or an uplink path so long as the electricfield profile of such waves in either direction is confined at least inpart or entirely within inner layers of cable 1850. In the presentillustration, downlink communications represents a communication pathfrom the pedestal 2004 to customer premises 2002, while uplinkcommunications represents a communication path from customer premises2002 to the pedestal 2004. In an embodiment where cable 1850 comprisesone of the embodiments of FIGS. 18G-18H, cable 1850 can also serve thepurpose of supplying power to the NID 2010 and 2020 and other equipmentof the customer premises 2002 and the pedestal 2004.

In customer premises 2002, DSL signals can originate from a DSL modem2006 (which may have a built-in router and which may provide wirelessservices such as WiFi to user equipment shown in the customer premises2002). The DSL signals can be supplied to NID 2010 by a twisted pairphone 2008. The NID 2010 can utilize the integrated waveguide 1602 tolaunch within cable 1850 guided electromagnetic waves 2014 directed tothe pedestal 2004 on an uplink path. In the downlink path, DSL signalsgenerated by the mini-DSLAM 2024 can flow through a twisted pair phoneline 2022 to NID 2020. The waveguide system 1602 integrated in the NID2020 can convert the DSL signals, or a portion thereof, from electricalsignals to guided electromagnetic waves 2014 that propagate within cable1850 on the downlink path. To provide full duplex communications, theguided electromagnetic waves 2014 on the uplink can be configured tooperate at a different carrier frequency and/or a different modulationapproach than the guided electromagnetic waves 2014 on the downlink toreduce or avoid interference. Additionally, on the uplink and downlinkpaths, the guided electromagnetic waves 2014 are guided by a coresection of cable 1850, as previously described, and such waves can beconfigured to have a field intensity profile that confines the guideelectromagnetic waves in whole or in part in the inner layers of cable1850. Although the guided electromagnetic waves 2014 are shown outsideof cable 1850, the depiction of these waves is for illustration purposesonly. For this reason, the guided electromagnetic waves 2014 are drawnwith “hash marks” to indicate that they are guided by the inner layersof cable 1850.

On the downlink path, the integrated waveguide system 1602 of NID 2010receives the guided electromagnetic waves 2014 generated by NID 2020 andconverts them back to DSL signals conforming to the requirements of theDSL modem 2006. The DSL signals are then supplied to the DSL modem 2006via a set of twisted pair wires of phone line 2008 for processing.Similarly, on the uplink path, the integrated waveguide system 1602 ofNID 2020 receives the guided electromagnetic waves 2014 generated by NID2010 and converts them back to DSL signals conforming to therequirements of the mini-DSLAM 2024. The DSL signals are then suppliedto the mini-DSLAM 2024 via a set of twisted pair wires of phone line2022 for processing. Because of the short length of phone lines 2008 and2022, the DSL modem 2008 and the mini-DSLAM 2024 can send and receiveDSL signals between themselves on the uplink and downlink at very highspeeds (e.g., 1 Gbps to 60 Gbps or more). Consequently, the uplink anddownlink paths can in most circumstances exceed the data rate limits oftraditional DSL communications over twisted pair phone lines.

Typically, DSL devices are configured for asymmetric data rates becausethe downlink path usually supports a higher data rate than the uplinkpath. However, cable 1850 can provide much higher speeds both on thedownlink and uplink paths. With a firmware update, a legacy DSL modem2006 such as shown in FIG. 20C can be configured with higher speeds onboth the uplink and downlink paths. Similar firmware updates can be madeto the mini-DSLAM 2024 to take advantage of the higher speeds on theuplink and downlink paths. Since the interfaces to the DSL modem 2006and mini-DSLAM 2024 remain as traditional twisted pair phone lines, nohardware change is necessary for a legacy DSL modem or legacy mini-DSLAMother than firmware changes and the addition of the NIDs 2010 and 2020to perform the conversion from DSL signals to guided electromagneticwaves 2014 and vice-versa. The use of NIDs enables a reuse of legacymodems 2006 and mini-DSLAMs 2024, which in turn can substantially reduceinstallation costs and system upgrades. For new construction, updatedversions of mini-DSLAMs and DSL modems can be configured with integratedwaveguide systems to perform the functions described above, therebyeliminating the need for NIDs 2010 and 2020 with integrated waveguidesystems. In this embodiment, an updated version of modem 2006 andupdated version of mini-DSLAM 2024 would connect directly to cable 1850and communicate via bidirectional guided electromagnetic wavetransmissions, thereby averting a need for transmission or reception ofDSL signals using twisted pair phone lines 2008 and 2022.

In an embodiment where use of cable 1850 between the pedestal 2004 andcustomer premises 2002 is logistically impractical or costly, NID 2010can be configured instead to couple to a cable 1850′ (similar to cable1850 of the subject disclosure) that originates from a waveguide 108 ona utility pole 118, and which may be buried in soil before it reachesNID 2010 of the customer premises 2002. Cable 1850′ can be used toreceive and transmit guided electromagnetic waves 2014′ between the NID2010 and the waveguide 108. Waveguide 108 can connect via waveguide 106,which can be coupled to base station 104. Base station 104 can providedata communication services to customer premises 2002 by way of itsconnection to central office 2030 over fiber 2026′. Similarly, insituations where access from the central office 2026 to pedestal 2004 isnot practical over a fiber link, but connectivity to base station 104 ispossible via fiber link 2026′, an alternate path can be used to connectto NID 2020 of the pedestal 2004 via cable 1850″ (similar to cable 1850of the subject disclosure) originating from pole 116. Cable 1850″ canalso be buried before it reaches NID 2020.

Turning now to FIGS. 20D-20F, block diagrams of example, non-limitingembodiments of antenna mounts that can be used in the communicationnetwork 2000 of FIG. 20C (or other suitable communication networks) inaccordance with various aspects described herein are shown. In someembodiments, an antenna mount 2052 can be coupled to a medium voltagepower line by way of an inductive power supply that supplies energy toone or more waveguide systems (not shown) integrated in the antennamount 2052 as depicted in FIG. 20D. The antenna mount 2052 can includean array of dielectric antennas 1901 (e.g., 16 antennas) such as shownby the top and side views depicted in FIG. 20F. The dielectric antennas1901 shown in FIG. 20F can be small in dimension as illustrated by apicture comparison between groups of dielectric antennas 1901 and aconventional ballpoint pen. In other embodiments, a pole mounted antenna2054 can be used as depicted in FIG. 20D. In yet other embodiments, anantenna mount 2056 can be attached to a pole with an arm assembly asshown in FIG. 20E. In other embodiments, an antenna mount 2058, depictedin FIG. 20E, can be placed on a top portion of a pole coupled to a cable1850 such as the cables as described in the subject disclosure.

The array of dielectric antennas 1901 in any of the antenna mounts ofFIGS. 20D-20E can include one or more waveguide systems as described inthe subject disclosure by way of FIGS. 1-20. The waveguide systems canbe configured to perform beam steering with the array of dielectricantennas 1901 (for transmission or reception of wireless signals).Alternatively, each dielectric antenna 1901 can be utilized as aseparate sector for receiving and transmitting wireless signals. Inother embodiments, the one or more waveguide systems integrated in theantenna mounts of FIGS. 20D-20E can be configured to utilizecombinations of the dielectric antennas 1901 in a wide range ofmulti-input multi-output (MIMO) transmission and reception techniques.The one or more waveguide systems integrated in the antenna mounts ofFIGS. 20D-20E can also be configured to apply communication techniquessuch as SISO, SIMO, MISO, SISO, signal diversity (e.g., frequency, time,space, polarization, or other forms of signal diversity techniques), andso on, with any combination of the dielectric antennas 1901 in any ofthe antenna mounts of FIGS. 20D-20E. In yet other embodiments, theantenna mounts of FIGS. 20D-20E can be adapted with two or more stacksof the antenna arrays shown in FIG. 20F.

FIGS. 21A and 21B describe embodiments for downlink and uplinkcommunications. Method 2100 of FIG. 21A can begin with step 2102 whereelectrical signals (e.g., DSL signals) are generated by a DSLAM (e.g.,mini-DSLAM 2024 of pedestal 2004 or from central office 2030), which areconverted to guided electromagnetic waves 2014 at step 2104 by NID 2020and which propagate on a transmission medium such as cable 1850 forproviding downlink services to the customer premises 2002. At step 2108,the NID 2010 of the customer premises 2002 converts the guidedelectromagnetic waves 2014 back to electrical signals (e.g., DSLsignals) which are supplied at step 2110 to customer premises equipment(CPE) such as DSL modem 2006 over phone line 2008 (as seen in FIG. 21A,step 2106 can optionally supply downlink guided electromagnetic wavesfrom the utility grid). Alternatively, or in combination, power and/orguided electromagnetic waves 2014′ can be supplied from a power line1850′ of a utility grid (having an inner waveguide as illustrated inFIG. 18G or 18H) to NID 2010 as an alternate or additional downlink(and/or uplink) path.

At step 2122 of method 2120 of FIG. 21B, the DSL modem 2006 can supplyelectrical signals (e.g., DSL signals) via phone line 2008 to NID 2010,which in turn at step 2124, converts the DSL signals to guidedelectromagnetic waves directed to NID 2020 by way of cable 1850. At step2128, the NID 2020 of the pedestal 2004 (or central office 2030)converts the guided electromagnetic waves 2014 back to electricalsignals (e.g., DSL signals) which are supplied at step 2129 to a DSLAM(e.g., mini-DSLAM 2024). Alternatively, or in combination, power andguided electromagnetic waves 2014′ can be supplied from a power line1850′ of a utility grid (having an inner waveguide as illustrated inFIG. 18G or 18H) to NID 2020 as an alternate or additional uplink(and/or downlink) path (see, for example, step 2126 of FIG. 21B).

Turning now to FIG. 21C, a flow diagram of an example, non-limitingembodiment of a method 2130 for inducing and receiving electromagneticwaves on a transmission medium is shown. At step 2132, the waveguides1865 and 1865′ of FIGS. 18N-18T can be configured to generate firstelectromagnetic waves from a first communication signal (supplied, forexample, by a communication device such as a base station), and induceat step 2134 the first electromagnetic waves with “only” a fundamentalwave mode at an interface of the transmission medium. In an embodiment,the interface can be an outer surface of the transmission medium asdepicted in FIGS. 18Q and 18R. In another embodiment, the interface canbe an inner layer of the transmission medium as depicted in FIGS. 18Sand 18T. At step 2136, the waveguides 1865 and 1865′ of FIGS. 18N-18Tcan be configured to receive second electromagnetic waves at aninterface of a same or different transmission medium described in FIG.21C. In an embodiment, the second electromagnetic waves can have “only”a fundamental wave mode. In other embodiments, the secondelectromagnetic waves may have a combination of wave modes such as afundamental and non-fundamental wave modes. At step 2138, a secondcommunication signal can be generated from the second electromagneticwaves for processing by, for example, a same or different communicationdevice. The embodiments of FIGS. 21C and 21D can be applied to anyembodiments described in the subject disclosure.

Turning now to FIG. 21D, a flow diagram of an example, non-limitingembodiment of a method 2140 for inducing and receiving electromagneticwaves on a transmission medium is shown. At step 2142, the waveguides1865 and 1865′ of FIGS. 18N-18W can be configured to generate firstelectromagnetic waves from a first communication signal (supplied, forexample, by a communication device), and induce at step 2144 secondelectromagnetic waves with “only” a non-fundamental wave mode at aninterface of the transmission medium. In an embodiment, the interfacecan be an outer surface of the transmission medium as depicted in FIGS.18Q and 18R. In another embodiment, the interface can be an inner layerof the transmission medium as depicted in FIGS. 18S and 18T. At step2146, the waveguides 1865 and 1865′ of FIGS. 18N-18W can be configuredto receive electromagnetic waves at an interface of a same or differenttransmission medium described in FIG. 21E. In an embodiment, theelectromagnetic waves can have “only” a non-fundamental wave mode. Inother embodiments, the electromagnetic waves may have a combination ofwave modes such as a fundamental and non-fundamental wave modes. At step2148, a second communication signal can be generated from theelectromagnetic waves for processing by, for example, a same ordifferent communication device. The embodiments of FIGS. 21E and 21F canbe applied to any embodiments described in the subject disclosure.

FIG. 21E illustrates a flow diagram of an example, non-limitingembodiment of a method 2150 for radiating signals from a dielectricantenna such as those shown in FIGS. 19A and 19N. Method 2150 can beginwith step 2152 where a transmitter such as waveguide system 1865′ ofFIG. 18T generates first electromagnetic waves including a firstcommunication signal. The first electromagnetic waves in turn induce atstep 2153 second electromagnetic waves on a core 1852 of a cable 1850coupled to a feed point of any of the dielectric antenna described inthe subject disclosure. The second electromagnetic waves are received atthe feed point at step 2154 and propagate at step 2155 to a proximalportion of the dielectric antenna. At step 2156, the secondelectromagnetic waves continue to propagate from the proximal portion ofthe dielectric antenna to an aperture of the antenna and thereby causeat step 2157 wireless signals to be radiated as previously described inrelation to FIGS. 19A-19N.

FIG. 21F illustrates a flow diagram of an example, non-limitingembodiment of a method 2160 for receiving wireless signals at adielectric antenna such as the dielectric antennas of FIG. 19A or 19N.Method 2160 can begin with step 2161 where the aperture of thedielectric antenna receives wireless signals. At step 2162, the wirelesssignals induce electromagnetic waves that propagate from the aperture tothe feed point of the dielectric antenna. The electromagnetic waves oncereceived at the feed point at step 2163, propagate at step 2164 to thecore of the cable coupled to the feed point. At step 2165, a receiversuch as the waveguide system 1865′ of FIG. 18T receives theelectromagnetic waves and generates therefrom at step 2166 a secondcommunication signal.

Methods 2150 and 2160 can be used to adapt the dielectric antennas ofFIGS. 19A, 19C, 19E, 19G-19I, and 19L-19O for bidirectional wirelesscommunications with other dielectric antennas such as the dielectricantennas 2040 shown in FIG. 20C, and/or for performing bidirectionalwireless communications with other communication devices such as aportable communication devices (e.g., cell phones, tablets, laptops),wireless communication devices situated in a building (e.g., aresidence), and so on. A microwave apparatus such as shown in FIG. 20Acan be configured with one or more cables 1850 that couple to aplurality of dielectric antennas 2040 as shown in FIG. 20C. In someembodiments, the dielectric antennas 2040 shown in FIG. 20C can beconfigured with yet more dielectric antennas (e.g., 19C, 19E, 19G-19I,and 19L-19O) to further expand the region of wireless communications bysuch antennas.

Methods 2150 and 2160 can be further adapted for use with the phasedarray 1976 of dielectric antennas 1901 of FIG. 19O by applyingincremental phase delays to portions of the antennas to steer far-fieldwireless signals emitted. Methods 2150 and 2160 can also be adapted foradjusting the far-field wireless signals generated by the dielectricantenna 1901 and/or an orientation of the dielectric antenna 1901utilizing the gimbal depicted in FIG. 19M (which may have controllableactuators) to improve reception of the far-field wireless signals by aremote system (such as another dielectric antenna 1901 coupled to awaveguide system). Additionally, the methods 2150 and 2160 can beadapted to receive instructions, messages or wireless signals from theremote system to enable the waveguide system receiving such signals byway of its dielectric antenna 1901 to perform adjustments of thefar-field signals.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIGS.21A-21F, it is to be understood and appreciated that the claimed subjectmatter is not limited by the order of the blocks, as some blocks mayoccur in different orders and/or concurrently with other blocks fromwhat is depicted and described herein. Moreover, not all illustratedblocks may be required to implement the methods described herein.

FIG. 21G illustrates a flow diagram of an example, non-limitingembodiment of a method 2170 for detecting and mitigating disturbancesoccurring in a communication network, such as, for example, the systemof FIGS. 16A and 16B. Method 2170 can begin with step 2172 where anetwork element, such as the waveguide system 1602 of FIGS. 16A-16B, canbe configured to monitor degradation of guided electromagnetic waves onan outer surface of a transmission medium, such as power line 1610. Asignal degradation can be detected according to any number of factorsincluding without limitation, a signal magnitude of the guidedelectromagnetic waves dropping below a certain magnitude threshold, asignal to noise ratio (SNR) dropping below a certain SNR threshold, aQuality of Service (QoS) dropping below one or more thresholds, a biterror rate (BER) exceeding a certain BER threshold, a packet loss rate(PLR) exceeding a certain PLR threshold, a ratio of reflectedelectromagnetic waves to forward electromagnetic waves exceeding acertain threshold, an unexpected change or alteration to a wave mode, aspectral change in the guided electromagnetic waves indicating an objector objects are causing a propagation loss or scattering of the guidedelectromagnetic waves (e.g., water accumulation on an outer surface ofthe transmission medium, a splice in the transmission medium, a brokentree limb, etc.), or any combinations thereof. A sensing device such as,the disturbance sensor 1604 b of FIG. 16A, can be adapted to perform oneor more of the above signal measurements and determine thereby whetherthe electromagnetic waves are experiencing signal degradation. Othersensing devices suitable for performing the above measurements arecontemplated by the subject disclosure.

If signal degradation is detected at step 2174, the network element canproceed to step 2176 where it can determine which object or objects maybe causing the degradation, and once detected, report the detectedobject(s) to the network management system 1601 of FIGS. 16A-16B. Objectdetection can be accomplished by spectral analysis or other forms ofsignal analysis, environmental analysis (e.g., barometric readings, raindetection, etc.), or other suitable techniques for detecting foreignobjects that may adversely affect propagation of electromagnetic wavesguided by the transmission medium. For example, the network element canbe configured to generate spectral data derived from an electromagneticwave received by the network element. The network element can thencompare the spectral data to a plurality of spectral profiles stored inits memory. The plurality of spectral profiles can be pre-stored in amemory of the network element, and can be used to characterize oridentify obstructions that may cause a propagation loss or signaldegradation when such obstructions are present on an outer surface ofthe transmission medium.

For example, an accumulation of water on an outer surface of atransmission medium, such as a thin layer of water and/or waterdroplets, may cause a signal degradation in electromagnetic waves guidedby the transmission medium that may be identifiable by a spectralprofile comprising spectral data that models such an obstruction. Thespectral profile can be generated in a controlled environment (such as alaboratory or other suitable testing environment) by collecting andanalyzing spectral data generated by test equipment (e.g., a waveguidesystem with spectrum analysis capabilities) when receivingelectromagnetic waves over an outer surface of a transmission mediumthat has been subjected to water (e.g., simulated rain water). Anobstruction such as water can generate a different spectral signaturethan other obstructions (e.g., a splice between transmission mediums). Aunique spectral signature can be used to identify certain obstructionsover others. With this technique, spectral profiles can be generated forcharacterizing other obstructions such as a fallen tree limb on thetransmission medium, a splice, and so on. In addition to spectralprofiles, thresholds can be generated for different metrics such as SNR,BER, PLR, and so on. These thresholds can be chosen by a serviceprovider according to desired performance measures for a communicationnetwork that utilizing guided electromagnetic waves for transport ofdata. Some obstructions may also be detected by other methods. Forexample, rain water may be detected by a rain detector coupled to anetwork element, fallen tree limbs may be detected by a vibrationdetector coupled to the network element, and so on.

If a network element does not have access to equipment to detect objectsthat may be causing a degradation of electromagnetic waves, then thenetwork element can skip step 2176 and proceed to step 2178 where itnotifies one or more neighboring network elements (e.g., other waveguidesystem(s) 1602 in a vicinity of the network element) of the detectedsignal degradation. If signal degradation is significant, the networkelement can resort to a different medium for communicating withneighboring network element(s), such as, for example, wirelesscommunications. Alternatively, the network element can substantiallyreduce the operating frequency of the guided electromagnetic waves(e.g., from 40 GHz to 1 GHz), or communicate with neighboring networkelements utilizing other guided electromagnetic waves operating at a lowfrequency, such as a control channel (e.g., 1 MHz). A low frequencycontrol channel may be much less susceptible to interference by theobject(s) causing the signal degradation at much higher operatingfrequencies.

Once an alternate means of communication is established between networkelements, at step 2180 the network element and neighboring networkelements can coordinate a process to adjust the guided electromagneticwaves to mitigate the detected signal degradation. The process caninclude, for example, a protocol for choosing which of the networkelements will perform the adjustments to the electromagnetic waves, thefrequency and magnitude of adjustments, and goals to achieve a desiredsignal quality (e.g., QoS, BER, PLR, SNR, etc.). If, for example, theobject causing the signal degradation is water accumulation on the outersurface of the transmission medium, the network elements can beconfigured to adjust a polarization of the electrical fields (e-fields)and/or magnetic fields (h-fields) of the electromagnetic waves to attaina radial alignment of the e-fields as shown in FIG. 21H. In particular,FIG. 21H presents a block diagram 2101 illustrating an example,non-limiting embodiment of an alignment of e-fields of anelectromagnetic wave to mitigate propagation losses due to wateraccumulation on a transmission medium in accordance with various aspectsdescribed herein. In this example, the longitudinal section of a cable,such as an insulated metal cable implementation of transmission medium125, is presented along with field vectors that illustrate the e-fieldsassociated with guided electromagnetic waves that propagate at 40 GHz.Stronger e-fields are presented by darker field vectors relative toweaker e-fields.

In one embodiment, an adjustment in polarization can be accomplished bygenerating a specific wave mode of the electromagnetic waves (e.g.,transverse magnetic (TM) mode, transverse electric (TE) mode, transverseelectromagnetic (TEM) mode, or a hybrid of a TM mode and TE mode alsoknown as an HE mode). Assuming, for example, that the network elementcomprises the waveguide system 1865′ of FIG. 18W, an adjustment in apolarization of e-fields can be accomplished by configuring two or moreMMIC's 1870 to alter a phase, frequency, amplitude or combinationsthereof of the electromagnetic waves generated by each MMIC 1870.Certain adjustments may cause, for example, the e-fields in the regionof the water film shown in FIG. 21H to align perpendicularly to thesurface of the water. Electric fields that are perpendicular (orapproximately perpendicular) to the surface of water will induce weakercurrents in the water film than e-fields parallel to the water film. Byinducing weaker currents, the electromagnetic waves propagatinglongitudinally will experience less propagation loss. Additionally, itis also desirable for the concentration of the e-fields to extend abovethe water film into the air. If the concentration of e-fields in the airremains high and the majority of the total field strength is in the airinstead of being concentrated in the region of the water and theinsulator, then propagation losses will also be reduced. For example,e-fields of electromagnetic waves that are tightly bound to aninsulation layer such as, Goubau waves (or TM00 waves—see block diagram2131 of FIG. 21K), will experience higher propagation losses even thoughthe e-fields may be perpendicular (or radially aligned) to the waterfilm because more of the field strength is concentrated in the region ofthe water.

Accordingly, electromagnetic waves with e-fields perpendicular (orapproximately perpendicular) to a water film having a higher proportionof the field strength in a region of air (i.e., above the water film)will experience less propagation loss than tightly bound electromagneticwaves having more field strength in the insulating or water layers orelectromagnetic waves having e-fields in the direction of propagationwithin the region of the water film that generate greater losses.

FIG. 21H depicts, in a longitudinal view of an insulated conductor,e-field for TM01 electromagnetic waves operating at 40 GHz. FIGS. 21Iand 21J, in contrast, depict cross-sectional views 2111 and 2121,respectively, of the insulated conductor of FIG. 21H illustrating thefield strength of e-fields in the direction of propagation of theelectromagnetic waves (i.e., e-fields directed out of the page of FIGS.21I and 21J). The electromagnetic waves shown in FIGS. 21I and 21J havea TM01 wave mode at 45 GHz and 40 GHz, respectively. FIG. 21I shows thatthe intensity of the e-fields in the direction of propagation of theelectromagnetic waves is high in a region between the outer surface ofthe insulation and the outer surface of the water film (i.e., the regionof the water film). The high intensity is depicted by a light color (thelighter the color the higher the intensity of the e-fields directed outof the page). FIG. 21I illustrates that there is a high concentration ofe-fields polarized longitudinally in the region of the water film, whichcauses high currents in the water film and consequently high propagationlosses. Thus, under certain circumstances, electromagnetic waves at 45GHz (having a TM01 wave mode) are less suitable to mitigate rain wateror other obstructions located on the outer surface of the insulatedconductor.

In contrast, FIG. 21J shows that the intensity of the e-fields in thedirection of propagation of the electromagnetic waves is weaker in theregion of the water film. The lower intensity is depicted by the darkercolor in the region of the water film. The lower intensity is a resultof the e-fields being polarized mostly perpendicular or radial to thewater film. The radially aligned e-fields also are highly concentratedin the region of air as shown in FIG. 21H. Thus, electromagnetic wavesat 40 GHz (having a TM01 wave mode) produce e-fields that induce lesscurrent in the water film than 45 GHz waves with the same wave mode.Accordingly, the electromagnetic waves of FIG. 21J exhibit propertiesmore suitable for reducing propagation losses due to a water film ordroplets accumulating on an outer surface of an insulated conductor.

Since the physical characteristics of a transmission medium can vary,and the effects of water or other obstructions on the outer surface ofthe transmission medium may cause non-linear effects, it may not alwaysbe possible to precisely model all circumstances so as to achieve thee-field polarization and e-field concentration in air depicted in FIG.21H on a first iteration of step 2182. To increase a speed of themitigation process, a network element can be configured to choose from alook-up table at step 2186 a starting point for adjustingelectromagnetic waves. In one embodiment, entries of the look-up tablecan be searched for matches to a type of object detected at step 2176(e.g., rain water). In another embodiment, the look-up table can besearched for matches to spectral data derived from the affectedelectromagnetic wave received by the network elements. Table entries canprovide specific parameters for adjusting electromagnetic waves (e.g.,frequency, phase, amplitude, wave mode, etc.) to achieve at least acoarse adjustment that achieves similar e-field properties as shown inFIG. 21H. A coarse adjustment can serve to improve the likelihood ofconverging on a solution that achieves the desirable propagationproperties previously discussed in relation to FIGS. 21H and 21J.

Once a coarse adjustment is made at step 2186, the network element candetermine at step 2184 whether the adjustment has improved signalquality to a desirable target. Step 2184 can be implemented by acooperative exchange between network elements. For example, suppose thenetwork element at step 2186 generates an adjusted electromagnetic waveaccording to parameters obtained from the look-up table and transmitsthe adjusted electromagnetic wave to a neighboring network element. Atstep 2184 the network element can determine whether the adjustment hasimproved signal quality by receiving feedback from a neighboring networkelement receiving the adjusted electromagnetic waves, analyzing thequality of the received waves according to agreed target goals, andproviding the results to the network element. Similarly, the networkelement can test adjusted electromagnetic waves received fromneighboring network elements and can provide feedback to the neighboringnetwork elements including the results of the analysis. While aparticular search algorithm is discussed above, other search algorithmssuch as a gradient search, genetic algorithm, global search or otheroptimization techniques can likewise be employed. Accordingly, steps2182, 2186 and 2184 represent an adjustment and testing processperformed by the network element and its neighbor(s).

With this in mind, if at step 2184 a network element (or its neighbors)determine that signal quality has not achieved one or more desiredparametric targets (e.g., SNR, BER, PLR, etc.), then incrementaladjustments can begin at step 2182 for each of the network element andits neighbors. At step 2182, the network element (and/or its neighbors)can be configured to adjust a magnitude, phase, frequency, wave modeand/or other tunable features of the electromagnetic waves incrementallyuntil a target goal is achieved. To perform these adjustments, a networkelement (and its neighbors) can be configured with the waveguide system1865′ of FIG. 18W. The network element (and its neighbors) can utilizetwo or more MMIC's 1870 to incrementally adjust one or more operationalparameters of the electromagnetic waves to achieve e-fields polarized ina particular direction (e.g., away from the direction of propagation inthe region of the water film). The two or more MMIC's 1870 can also beconfigured to incrementally adjust one or more operational parameters ofthe electromagnetic waves that achieve e-fields having a highconcentration in a region of air (outside the obstruction).

The iteration process can be a trial-and-error process coordinatedbetween network elements to reduce a time for converging on a solutionthat improves upstream and downstream communications. As part of thecoordination process, for example, one network element can be configuredto adjust a magnitude but not a wave mode of the electromagnetic waves,while another network element can be configured to adjust the wave modeand not the magnitude. The number of iterations and combination ofadjustments to achieve desirable properties in the electromagnetic wavesto mitigate obstructions on an outer surface of a transmission mediumcan be established by a service provider according to experimentationand/or simulations and programmed into the network elements.

Once the network element(s) detect at step 2184 that signal quality ofupstream and downstream electromagnetic waves has improved to adesirable level that achieves one or more parametric targets (e.g. SNR,BER, PLR, etc.), the network elements can proceed to step 2188 andresume communications according to the adjusted upstream and downstreamelectromagnetic waves. While communications take place at step 2188, thenetwork elements can be configured to transmit upstream and downstreamtest signals based on the original electromagnetic waves to determine ifthe signal quality of such waves has improved. These test signals can betransmitted at periodic intervals (e.g., once every 30 seconds or othersuitable periods). Each network element can, for example, analyzespectral data of the received test signals to determine if they achievea desirable spectral profile and/or other parametric target (e.g. SNR,BER, PLR, etc.). If the signal quality has not improved or has improvednominally, the network elements can be configured to continuecommunications at step 2188 utilizing the adjusted upstream anddownstream electromagnetic waves.

If, however, signal quality has improved enough to revert back toutilizing the original electromagnetic waves, then the networkelement(s) can proceed to step 2192 to restore settings (e.g., originalwave mode, original magnitude, original frequency, original phase,original spatial orientation, etc.) that produce the originalelectromagnetic waves. Signal quality may improve as a result of aremoval of the obstruction (e.g., rain water evaporates, field personnelremove a fallen tree limb, etc.). At step 2194, the network elements caninitiate communications utilizing the original electromagnetic waves andperform upstream and downstream tests. If the network elements determineat step 2196 from tests performed at step 2194 that signal quality ofthe original electromagnetic waves is satisfactory, then the networkelements can resume communications with the original electromagneticwaves and proceed to step 2172 and subsequent steps as previouslydescribed.

A successful test can be determined at step 2196 by analyzing testsignals according to parametric targets associated with the originalelectromagnetic waves (e.g., BER, SNR, PLR, etc.). If the testsperformed at step 2194 are determined to be unsuccessful at step 2196,the network element(s) can proceed to steps 2182, 2186 and 2184 aspreviously described. Since a prior adjustment to the upstream anddownstream electromagnetic waves may have already been determinedsuccessfully, the network element(s) can restore the settings used forthe previously adjusted electromagnetic waves. Accordingly, a singleiteration of any one of steps 2182, 2186 and 2184 may be sufficient toreturn to step 2188.

It should be noted that in some embodiments restoring the originalelectromagnetic waves may be desirable if, for example, data throughputwhen using the original electromagnetic waves is better than datathroughput when using the adjusted electromagnetic waves. However, whendata throughput of the adjusted electromagnetic waves is better orsubstantially close to the data throughput of the originalelectromagnetic waves, the network element(s) may instead be configuredto continue from step 2188.

It is also noted that although FIGS. 21H and 21K describe a TM01 wavemode, other wave modes (e.g., HE waves, TE waves, TEM waves, etc.) orcombination of wave modes may achieve the desired effects shown in FIG.21H. Accordingly, a wave mode singly or in combination with one or moreother wave modes may generate electromagnetic waves with e-fieldproperties that reduce propagation losses as described in relation toFIGS. 21H and 21J. Such wave modes are therefore contemplated aspossible wave modes the network elements can be configured to produce.

It is further noted that method 2170 can be adapted to generate at steps2182 or 2186 other wave modes that may not be subject to a cutofffrequency. For example, FIG. 21L depicts a block diagram 2141 of anexample, non-limiting embodiment of electric fields of a hybrid wave inaccordance with various aspects described herein. Waves having an HEmode have linearly polarized e-fields which point away from a directionof propagation of electromagnetic waves and can be perpendicular (orapproximately perpendicular) to a region of obstruction (e.g., waterfilm shown in FIGS. 21H-21J). Waves with an HE mode can be configured togenerate e-fields that extend substantially outside of an outer surfaceof an insulated conductor so that more of the total accumulated fieldstrength is in air. Accordingly, some electromagnetic waves having an HEmode can exhibit properties of a large wave mode with e-fieldsorthogonal or approximately orthogonal to a region of obstruction. Asdescribed earlier, such properties can reduce propagation losses.Electromagnetic waves having an HE mode also have the unique propertythat they do not have a cutoff frequency (i.e., they can operate nearDC) unlike other wave modes which have non-zero cutoff frequencies.

Turning now to FIG. 21M, a block diagram 2151 illustrating an example,non-limiting embodiment of electric field characteristics of a hybridwave versus a Goubau wave in accordance with various aspects describedherein is shown. Diagram 2153 shows a distribution of energy betweenHE11 mode waves and Goubau waves for an insulated conductor. The energyplots of diagram 2153 assume that the amount of power used to generatethe Goubau waves is the same as the HE11 waves (i.e., the area under theenergy curves is the same). In the illustration of diagram 2153, Goubauwaves have a steep drop in power when Goubau waves extend beyond theouter surface of an insulated conductor, while HE11 waves have asubstantially lower drop in power beyond the insulation layer.Consequently, Goubau waves have a higher concentration of energy nearthe insulation layer than HE 11 waves. Diagram 2155 depicts similarGoubau and HE11 energy curves when a water film is present on the outersurface of the insulator. The difference between the energy curves ofdiagrams 2153 and 2155 is that the drop in power for the Goubau and theHE11 energy curves begins on an outer edge of the insulator for diagram2153 and on an outer edge of the water film for diagram 2155. The energycurves diagrams 2153 and 2155, however, depict the same behavior. Thatis, the electric fields of Goubau waves are tightly bound to theinsulation layer, which when exposed to water results in greaterpropagation losses than electric fields of HE11 waves having a higherconcentration outside the insulation layer and the water film. Theseproperties are depicted in the HE11 and Goubau diagrams 2157 and 2159,respectively.

By adjusting an operating frequency of HE11 waves, e-fields of HE11waves can be configured to extend substantially above a thin water filmas shown in block diagram 2161 of FIG. 21N having a greater accumulatedfield strength in areas in the air when compared to fields in theinsulator and a water layer surrounding the outside of the insulator.FIG. 21N depicts a wire having a radius of 1 cm and an insulation radiusof 1.5 cm with a dielectric constant of 2.25. As the operating frequencyof HE11 waves is reduced, the e-fields extend outwardly expanding thesize of the wave mode. At certain operating frequencies (e.g., 3GHz—mode expansion clearly visible) the wave mode expansion can besubstantially greater than the diameter of the insulated wire and anyobstructions that may be present on the insulated wire (compare toexamples showing 10 GHz and 6 GHz in FIG. 21N).

By having e-fields that are perpendicular to a water film and by placingmost of its energy outside the water film, HE11 waves have lesspropagation loss than Goubau waves when a transmission medium issubjected to water or other obstructions. Although Goubau waves haveradial e-fields which are desirable, the waves are tightly coupled tothe insulation layer, which results in the e-fields being highlyconcentrated in the region of an obstruction. Consequently, Goubau wavesare still subject to high propagation losses when an obstruction such asa water film is present on the outer surface of an insulated conductor.

Turning now to FIGS. 22A and 22B, block diagrams (associated with HE11Mode Launcher) illustrating example, non-limiting embodiments of awaveguide system 2200 for launching hybrid waves in accordance withvarious aspects described herein is shown. The waveguide system 2200 cancomprise probes 2202 coupled to a slideable or rotatable mechanism 2204that enables the probes 2202 to be placed at different positions ororientations relative to an outer surface of an insulated conductor2208. The mechanism 2204 can comprise a coaxial feed 2206 or othercoupling that enables transmission of electromagnetic waves by theprobes 2202. The coaxial feed 2206 can be placed at a position on themechanism 2204 so that the path difference between the probes 2202 isone-half a wavelength or some odd integer multiple thereof. When theprobes 2202 generate electromagnetic signals of opposite phase,electromagnetic waves can be induced on the outer surface of theinsulated conductor 2208 having a hybrid mode (such as an HE11 mode).

The mechanism 2204 can also be coupled to a motor or other actuator (notshown) for moving the probes 2202 to a desirable position. In oneembodiment, for example, the waveguide system 2200 can comprise acontroller that directs the motor to rotate the probes 2202 (assumingthey are rotatable) to a different position (e.g., east and west) togenerate electromagnetic waves that have a horizontally polarized HE11mode. To guide the electromagnetic waves onto the outer surface of theinsulated conductor 2208, the waveguide system 2200 can further comprisea tapered horn 2210 shown in FIG. 22B. The tapered horn 2210 can becoaxially aligned with the insulated conductor 2208. To reduce thecross-sectional dimension of the tapered horn 2210, an additionalinsulation layer (not shown) can placed on the insulated conductor 2208.The additional insulation layer can be similar to the tapered insulationlayer 1879 shown in FIGS. 18G and 18H. The additional insulation layercan have a tapered end that points away from the tapered horn 2210. Thetapered insulation layer 1879 can reduce a size of an initialelectromagnetic wave launched according to an HE11 mode. As theelectromagnetic waves propagate towards the tapered end of theinsulation layer, the HE11 mode expands until it reaches its full size.In other embodiments, the waveguide system 2200 may not need to use thetapered insulation layer 1879.

HE11 mode waves can be used to mitigate obstructions such as rain water.For example, suppose that rain water has caused a water film to surroundan outer surface of the insulated conductor 2208. Further assume thatwater droplets have collected at the bottom of the insulated conductor2208. The water film occupies a small fraction of the total HE11 wave.Also, by having horizontally polarized HE11 waves, the water dropletsare in a least-intense area of the HE11 waves reducing losses caused bythe droplets. Consequently, the HE11 waves experience much lowerpropagation losses than Goubau waves or waves having a mode that istightly coupled to the insulated conductor 2208 and thus greater energyin the areas occupied by the water.

It is submitted that the waveguide system 2200 of FIGS. 22A-22B can bereplaced with other waveguide systems of the subject disclosure capableof generating electromagnetic waves having an HE mode. For example, thewaveguide system 1865′ of FIG. 18K can be configured to generateelectromagnetic waves having an HE mode. In an embodiment, two or moreMMICs 1870 of the waveguide system 1865′ can be configured to generateelectromagnetic waves of opposite phase to generate polarized e-fieldssuch as those present in an HE mode. In another embodiment, differentpairs of MMICs 1870 can be selected to generate HE waves that arepolarized at different spatial positions (e.g., north and south, westand east, northwest and southeast, northeast and southeast, or othersub-fractional coordinates). Additionally, the waveguide systems ofFIGS. 18D-18K can be configured to launch electromagnetic waves havingan HE mode onto the core 1852 of one or more embodiments of cable 1850suitable for propagating HE mode waves.

Although HE waves can have desirable characteristics for mitigatingobstructions on a transmission medium, it is submitted that certain wavemodes having a cutoff frequency (e.g., TE modes, TM modes orcombinations thereof) may also exhibit waves that are sufficiently largeand have polarized e-fields that are orthogonal (or approximatelyorthogonal) to a region of an obstruction enabling their use formitigating propagation losses caused by the obstruction.

Turning to the illustration of FIG. 23A, the waveguide 2522 covers afirst region 2506 of a core 2528. Within the first region 2506,waveguide 2522 has an outer surface 2522A and an inner surface 2523. Theinner surface 2523 of the waveguide 2522 can be constructed from ametallic material or other material that reflects electromagnetic wavesand thereby enables the waveguide 2522 to be configured at step 2404 toguide the first electromagnetic wave 2502 towards the core 2528. Thecore 2528 can comprise a dielectric core (as described in the subjectdisclosure) that extends to the inner surface 2523 of the waveguide2522. In other embodiments, the dielectric core can be surrounded bycladding (such as shown in FIG. 18A), whereby the cladding extends tothe inner surface 2523 of the waveguide 2522. In yet other embodiments,the core 2528 can comprise an insulated conductor, where the insulationextends to the inner surface 2523 of the waveguide 2522. In thisembodiment, the insulated conductor can be a power line, a coaxialcable, or other types of insulated conductors.

In the first region 2506, the core 2528 comprises an interface 2526 forreceiving the first electromagnetic wave 2502. In one embodiment, theinterface 2526 of the core 2528 can be configured to reduce reflectionsof the first electromagnetic wave 2502. In one embodiment, the interface2526 can be a tapered structure to reduce reflections of the firstelectromagnetic wave 2502 from a surface of the core 2528. Otherstructures can be used for the interface 2526. For example, theinterface 2526 can be partially tapered with a rounded point.Accordingly, any structure, configuration, or adaptation of theinterface 2526 that can reduced reflections of the first electromagneticwave 2502 is contemplated by the subject disclosure. The firstelectromagnetic wave 2502 induces (or otherwise generates) a secondelectromagnetic wave 2504 that propagates within the core 2528 in thefirst region 2506 covered by the waveguide 2522. The inner surface 2523of the waveguide 2522 confines the second electromagnetic wave 2504within the core 2528.

A second region 2508 of the core 2528 is not covered by the waveguide2522, and is thereby exposed to the environment (e.g., air). In thesecond region 2508, the second electromagnetic wave 2504 expandsoutwardly beginning from the discontinuity between the edge of thewaveguide 2522 and the exposed core 2528. To reduce the radiation intothe environment from the second electromagnetic wave 2504, the core 2528can be configured to have a tapered structure 2520. As the secondelectromagnetic wave 2504 propagates along the tapered structure 2520,the second electromagnetic wave 2504 remains substantially bound to thetapered structure 2520 thereby reducing radiation losses. The taperedstructure 2520 ends at a transition from the second region 2508 to athird region 2510. In the third region, the core has a cylindricalstructure 2529 having a diameter equal to the endpoint of the taperedstructure 2520 at the juncture between the second region 2508 and thethird region 2510. In the third region 2510 of the core 2528, the secondelectromagnetic wave 2504 experiences a low propagation loss. In oneembodiment, this can be accomplished by selecting a diameter of the core2528 that enables the second electromagnetic wave 2504 to be looselybound to the outer surface of the core 2528 in the third region 2510.Alternatively, or in combination, propagation losses of the secondelectromagnetic wave 2504 can be reduced by configuring the MMICs 2524to adjust a wave mode, wave length, operating frequency, or otheroperational parameter of the first electromagnetic wave 2502.

FIG. 24 illustrates a portion of the waveguide 2522 of FIG. 23A depictedas a cylindrical ring (that does not show the MMICs 2524 or the taperedstructure 2526 of FIG. 23A). In the simulations, a first electromagneticwave is injected at the endpoint of the core 2528 shown in FIG. 24. Thesimulation assumes no reflections of the first electromagnetic wavebased on an assumption that a tapered structure 2526 (or other suitablestructure) is used to reduce such reflections. The simulations are shownas two longitudinal cross-sectional views of the core 2528 covered inpart by waveguide section 2523A, and an orthogonal cross-sectional viewof the core 2528. In the case of the longitudinal cross-sectional views,one of the illustrations is a blown up view of a portion of the firstillustration.

As can be seen from the simulations, electromagnetic wave fields 2532 ofthe second electromagnetic wave 2504 are confined within the core 2528by the inner surface 2523 of the waveguide section 2523A. As the secondelectromagnetic wave 2504 enters the second region 2508 (no longercovered by the waveguide section 2523A), the tapered structure 2520reduces radiation losses of the electromagnetic wave fields 2532 as itexpands over the outer tapered surface of the core 2528. As the secondelectromagnetic wave 2504 enters the third region 2510, theelectromagnetic wave fields 2532 stabilize and thereafter remain looselycoupled to the core 2528 (depicted in the longitudinal and orthogonalcross-sectional views), which reduces propagation losses.

FIG. 23B provides an alternative embodiment to the tapered structure2520 in the second region 2508. The tapered structure 2520 can beavoided by extending the waveguide 2522 into the second region 2508 witha tapered structure 2522B and maintaining the diameter of the core 2528throughout the first, second and third regions 2506, 2508 and 2510 ofthe core 2528 as depicted in FIG. 23B. The horn structure 2522B can beused to reduce radiation losses of the second electromagnetic wave 2504as the second electromagnetic wave 2504 transitions from the firstregion 2506 to the second region 2508. In the third region 2510, thecore 2528 is exposed to the environment. As noted earlier, the core 2528is configured in the third region 2510 to reduce propagation losses bythe second electromagnetic wave 2504. In one embodiment, this can beaccomplished by selecting a diameter of the core 2528 that enables thesecond electromagnetic wave 2504 to be loosely bound to the outersurface of the core 2528 in the third region 2510. Alternatively, or incombination, propagation losses of the second electromagnetic wave 2504can be reduced by adjusting a wave mode, wave length, operatingfrequency, or other performance parameter of the first electromagneticwave 2502.

The waveguides 2522 of FIGS. 23A and 23B can also be adapted forreceiving electromagnetic waves. For example, the waveguide 2522 of FIG.23A can be adapted to receive an electromagnetic wave at step 2412. Thiscan be represented by an electromagnetic wave 2504 propagating in thethird region 2510 from east to west (orientation shown at bottom rightof FIGS. 23A-23B) towards the second region 2508. Upon reaching thesecond region 2508, the electromagnetic wave 2504 gradually becomes moretightly coupled to the tapered structure 2520. When it reaches theboundary between the second region 2508 and the first region 2506 (i.e.,the edge of the waveguide 2522), the electromagnetic wave 2504propagates within the core 2528 confined by the inner surface 2523 ofthe waveguide 2522. Eventually the electromagnetic wave 2504 reaches anendpoint of the tapered interface 2526 of the core 2528 and radiates asa new electromagnetic wave 2502 which is guided by the inner surface2523 of the waveguide 2522.

One or more antennas of the MMICs 2524 can be configured to receive theelectromagnetic wave 2502 thereby converting the electromagnetic wave2502 to an electrical signal at step 2414 which can be processed by aprocessing device (e.g., a receiver circuit and microprocessor). Toprevent interference between electromagnetic waves transmitted by theMMICs 2524, a remote waveguide system that transmitted theelectromagnetic wave 2504 that is received by the waveguide 2522 of FIG.23A can be adapted to transmit the electromagnetic wave 2504 at adifferent operating frequency, different wave mode, different phase, orother adjustable operational parameter to avoid interference.Electromagnetic waves can be received by the waveguide 2522 of FIG. 23Bin a similar manner as described above.

Turning now to FIG. 23C, the waveguide 2522 of FIG. 23B can be adaptedto support transmission mediums 2528 that have no endpoints such asshown in FIG. 23C. In this illustration, the waveguide 2522 comprises achamber 2525 in a first region 2506 of the core 2528. The chamber 2525creates a gap 2527 between an outer surface 2521 of the core 2528 andthe inner surface 2523 of the waveguide 2522. The gap 2527 providessufficient room for placement of the MMICs 2524 on the inner surface2523 of the waveguide 2522. To enable the waveguide 2522 to receiveelectromagnetic waves from either direction, the waveguide 2522 can beconfigured with symmetrical regions: 2508 and 2508′, 2510 and 2510′, and2512, and 2512′. In the first region 2506, the chamber 2525 of thewaveguide 2522 has two tapered structures 2522B′ and 2522B″. Thesetapered structures 2522B′ and 2522B″ enable an electromagnetic wave togradually enter or exit the chamber 2525 from either direction of thecore 2528. The MMICs 2524 can be configured with directional antennas tolaunch a first electromagnetic wave 2502 directed from east-to-west orfrom west-to-east in relation to the longitudinal view of the core 2528.Similarly, the directional antennas of the MMICs 2524 can be configuredto receive an electromagnetic waves propagating longitudinally on thecore 2528 from east-to-west or from west-to-east. The process fortransmitting electromagnetic waves is similar to that described for FIG.23B depending on whether the directional antennas of the MMICs 2524 aretransmitting from east-to-west or from west-to-east.

Although not shown, the waveguide 2522 of FIG. 23C can be configuredwith a mechanism such as one or more hinges that enable splitting thewaveguide 2522 into two parts that can be separated. The mechanism canbe used to enable installation of the waveguide 2522 onto a core 2528without endpoints. Other mechanisms for installation of the waveguide2522 of FIG. 23C on a core 2528 are contemplated by the subjectdisclosure. For example, the waveguide 2522 can be configured with aslot opening that spans the entire waveguide structure longitudinally.In a slotted design of the waveguide 2522, the regions 2522C′ and 2522Cof the waveguide 2522 can be configured so that the inner surface 2523of the waveguide 2522 is tightly coupled to the outer surface of thecore 2528. The tight coupling between the inner surface 2523 of thewaveguide 2522 the outer surface of the core 2528 prevents sliding ormovement of the waveguide 2522 relative to the core 2528. A tightcoupling in the regions 2522C′ and 2522C can also be applied to a hingeddesign of the waveguide 2522.

The waveguides 2522 shown in FIGS. 23A, 23B and 25C can be adapted toperform one or more embodiments described in other figures of thesubject disclosure. Accordingly, it is contemplated that suchembodiments can be applied to the waveguide 2522 of FIGS. 23A, 23B and23C. Additionally, any adaptations in the subject disclosure of a corecan be applied to the waveguide 2522 of FIGS. 23A, 23B and 23C.

It is further noted that the waveguide launchers 2522 of FIGS. 23A-23Cand/or other waveguide launchers described and shown in the figures ofthe subject disclosure (e.g., FIGS. 7-14, 18D-18K, 22A-22B, 23A-23C, 24and other drawings) and any methods thereof can be adapted to generatealong a transmission medium having an outer surface composed of, forexample, a dielectric material (e.g., insulation, oxidation, or othermaterial with dielectric properties) a single wave mode or combinationof wave modes that reduce propagation losses when propagating through asubstance, such as a liquid (e.g., water produced by humidity, snow,dew, sleet and/or rain), disposed on the outer surface of thetransmission medium.

Referring now to FIG. 25A, there is illustrated a diagram of an example,non-limiting embodiment of a waveguide device 2522 in accordance withvarious aspects described herein. In the illustration of FIG. 25A, thewaveguide device 2522 is coupled to a transmission medium 2542comprising a conductor 2543 and insulation layer 2543, which togetherform an insulated conductor. Although not shown, the waveguide device2522 can be constructed in two halves, which can be connected togetherat one longitudinal end with one or more mechanical hinges to enableopening a longitudinal edge at an opposite end of the one or more hingesfor placement of the waveguide device 2522 over the transmission medium2542. Once placed, one or more latches at the longitudinal edge oppositethe one or more hinges can be used to secure the waveguide device 2522to the transmission medium 2542. Other embodiments for coupling thewaveguide device 2522 to the transmission medium 2542 can be used andare therefore contemplated by the subject disclosure.

The chamber 2525 of the waveguide device 2522 of FIG. 25A includes adielectric material 2544′. The dielectric material 2544′ in the chamber2525 can have a dielectric constant similar to the dielectric constantof the dielectric layer 2544 of the insulated conductor. Additionally, adisk 2525′ having a center-hole 2525″ can be used to divide the chamber2525 in two halves for transmission or reception of electromagneticwaves. The disk 2525′ can be constructed of a material (e.g., carbon,metal or other reflective material) that does not allow electromagneticwaves to progress between the halves of the chamber 2525. The MMICs2524′ can be located inside the dielectric material 2544′ of the chamber2525 as shown in FIG. 25A. Additionally, the MMICs 2524′ can be locatednear an outer surface of the dielectric layer 2543 of the transmissionmedium 2542. FIG. 25A shows an expanded view 2524A′ of an MMIC 2524′that includes an antenna 2524B′ (such as a monopole antenna, dipoleantenna or other antenna) that can be configured to be longitudinallyaligned with the outer surface of the dielectric layer 2543 of thetransmission medium 2542. The antenna 2524B′ can be configured toradiate signals that have a longitudinal electric field directed east orwest as will be discussed shortly. It will be appreciated that otherantenna structures that can radiate signals that have a longitudinalelectric field can be used in place of the dipole antenna 2524B′ of FIG.25A.

It will be appreciated that although two MMICs 2524′ are shown in eachhalf of the chambers 2525 of the waveguide device 2522, more MMICs canbe used. For example, FIG. 18K shows a transverse cross-sectional viewof a cable (such as the transmission medium 2542) surrounded by awaveguide device with 8 MMICs located in positions: north, south, east,west, northeast, northwest, southeast, and southwest. The two MMICs2524′ shown in FIG. 25A can be viewed, for illustration purposes, asMMICs 2524′ located in the north and south positions shown in FIG. 18K.The waveguide device 2522 of FIG. 25A can be further configured withMMICs 2524′ at western and eastern positions as shown in FIG. 18K.Additionally, the waveguide device 2522 of FIG. 25A can be furtherconfigured with MMICs at northwestern, northeastern, southwestern andsoutheastern positions as shown in FIG. 18K. Accordingly, the waveguidedevice 2522 can be configured with more than the 2 MMICs shown in FIG.25A.

With this in mind, attention is now directed to FIGS. 25B, 25C, 25D,which illustrate diagrams of example, non-limiting embodiments of wavemodes and electric field plots in accordance with various aspectsdescribed herein. FIG. 25B illustrates the electric fields of a TM01wave mode. The electric fields are illustrated in a transversecross-sectional view (top) and a longitudinal cross-sectional view(below) of a coaxial cable having a center conductor with an externalconductive shield separated by insulation. FIG. 25C illustrates theelectric fields of a TM11 wave mode. The electric fields are alsoillustrated in a transverse cross-sectional view and a longitudinalcross-sectional view of a coaxial cable having a center conductor withan external conductive shield separated by an insulation. FIG. 25Dfurther illustrates the electric fields of a TM21 wave mode. Theelectric fields are illustrated in a transverse cross-sectional view anda longitudinal cross-sectional view of a coaxial cable having a centerconductor with an external conductive shield separated by an insulation.

As shown in the transverse cross-sectional view, the TM01 wave mode hascircularly symmetric electric fields (i.e., electric fields that havethe same orientation and intensity at different azimuthal angles), whilethe transverse cross-sectional views of the TM11 and TM21 wave modesshown in FIGS. 25C-25D, respectively, have non-circularly symmetricelectric fields (i.e., electric fields that have different orientationsand intensities at different azimuthal angles). Although the transversecross-sectional views of the TM11 and TM21 wave modes havenon-circularly symmetric electric fields, the electric fields in thelongitudinal cross-sectional views of the TM01, TM11 and TM21 wave modesare substantially similar with the exception that that the electricfield structure of the TM11 wave mode has longitudinal electric fieldsabove the conductor and below the conductor that point in oppositelongitudinal directions, while the longitudinal electric fields abovethe conductor and below the conductor for the TM01 and TM21 wave modespoint in the same longitudinal direction.

The longitudinal cross-sectional views of the coaxial cable of FIGS.25B, 25C and 25D can be said to have a similar structural arrangement tothe longitudinal cross-section of the waveguide device 2522 in region2506′ shown in FIG. 25A. Specifically, in FIGS. 25B, 25C and 25D thecoaxial cable has a center conductor and a shield separated byinsulation, while region 2506′ of the waveguide device 2522 has a centerconductor 2543, a dielectric layer 2544, covered by the dielectricmaterial 2544′ of the chamber 2525, and shielded by the reflective innersurface 2523 of the waveguide device 2522. The coaxial configuration inregion 2506′ of the waveguide device 2522 continues in the taperedregion 2506″ of the waveguide device 2522. Similarly, the coaxialconfiguration continues in regions 2508 and 2510 of the waveguide device2522 with the exception that no dielectric material 2544′ is present inthese regions other than the dielectric layer 2544 of the transmissionmedium 2542. At the outer region 2512, the transmission medium 2542 isexposed to the environment (e.g., air) and thus the coaxialconfiguration is no longer present.

As noted earlier, the electric field structure of a TM01 wave mode iscircularly symmetric in a transverse cross-sectional view of the coaxialcable shown in FIG. 25B. For illustration purposes, it will be assumedthat the waveguide device 2522 of FIG. 25A has 4 MMICs located innorthern, southern, western and eastern locations as depicted in FIG.18K. In this configuration, and with an understanding of thelongitudinal and transverse electric field structures of the TM01 wavemode shown in FIG. 25B, the 4 MMICs 2524′ of the waveguide device 2522in FIG. 25A can be configured to launch from a common signal source aTM01 wave mode on the transmission medium 2542. This can be accomplishedby configuring the north, south, east and west MMICs 2524′ to launchwireless signals with the same phase (polarity). The wireless signalsgenerated by the 4 MMICs 2524′ combine via superposition of theirrespective electric fields in the dielectric material 2544′ of thechamber 2525 and the dielectric layer 2544 (since both dielectricmaterials have similar dielectric constants) to form a TM01electromagnetic wave 2502′ bound to these dielectric materials with theelectric field structure shown in longitudinal and transverse views ofFIG. 25B.

The electromagnetic wave 2502′ having the TM01 wave mode in turnpropagates toward the tapered structure 2522B of the waveguide device2522 and thereby becomes an electromagnetic wave 2504′ embedded withinthe dielectric layer 2544 of the transmission medium 2542′ in region2508. In the tapered horn section 2522D the electromagnetic wave 2504′having the TM01 wave mode expands in region 2510 and eventually exitsthe waveguide device 2522 without change to the TM01 wave mode.

In another embodiment, the waveguide device 2522 can be configured tolaunch a TM11 wave mode having a vertical polarity in region 2506′. Thiscan be accomplished by configuring the MMIC 2524′ in the northernposition to radiate from a signal source a first wireless signal havinga phase (polarity) opposite to the phase (polarity) of a second wirelesssignal radiated from the same signal source by the southern MMIC 2524′.These wireless signals combine via superposition of their respectiveelectric fields to form an electromagnetic wave having a TM11 wave mode(vertically polarized) bound to the dielectric materials 2544′ and 2544with the electric field structures shown in the longitudinal andtransverse cross-sectional views shown in FIG. 25C. Similarly, thewaveguide device 2522 can be configured to launch a TM11 wave modehaving a horizontal polarity in region 2506′. This can be accomplishedby configuring the MMIC 2524′ in the eastern position to radiate a firstwireless signal having a phase (polarity) opposite to the phase(polarity) of a second wireless signal radiated by the western MMIC2524′.

These wireless signals combine via superposition of their respectiveelectric fields to form an electromagnetic wave having a TM11 wave mode(horizontally polarized) bound to the dielectric materials 2544′ and2544 with the electric field structures shown in the longitudinal andtransverse cross-sectional views shown in FIG. 25C (but with ahorizontal polarization). Since the TM11 wave mode with horizontal andvertical polarizations are orthogonal (i.e., a dot product ofcorresponding electric field vectors between any pair of these wavemodes at each point of space and time produces a summation of zero), thewaveguide device 2522 can be configured to launch these wave modessimultaneously without interference, thereby enabling wave mode divisionmultiplexing. It is further noted that the TM01 wave mode is alsoorthogonal to the TM11 and TM21 wave modes.

While the electromagnetic wave 2502′ or 2504′ having the TM11 wave modepropagates within the confines of the inner surfaces 2523 of thewaveguide device 2522 in regions 2506′, 2506″, 2508 and 2510, the TM11wave mode remains unaltered. However, when the electromagnetic wave2504′ having the TM11 wave mode exits the waveguide device 2522 inregion 2512 the inner wall 2523 is no longer present and the TM11 wavemode becomes a hybrid wave mode, specifically, an EH11 wave mode(vertically polarized, horizontally polarized, or both if twoelectromagnetic waves are launched in region 2506′).

In yet other embodiments, the waveguide device 2522 can also beconfigured to launch a TM21 wave mode in region 2506′. This can beaccomplished by configuring the MMIC 2524′ in the northern position toradiate from a signal source a first wireless signal having a phase(polarity) that is in phase (polarity) to a second wireless signalgenerated from the same signal source by the southern MMIC 2524′. At thesame time, the MMIC 2524′ in the western position is configured toradiate from the same signal source a third wireless signal that is inphase with a fourth wireless signal radiated from the same signal sourceby the MMIC 2524′ located in the eastern position. The north and southMMICs 2524′, however, generate first and second wireless signals ofopposite polarity to the polarity of the third and fourth wirelesssignals generated by the western and eastern MMICs 2524′. The fourwireless signals of alternating polarity combine via superposition oftheir respective electric fields to form an electromagnetic wave havinga TM21 wave mode bound to the dielectric materials 2544′ and 2544 withthe electric field structures shown in the longitudinal and transversecross-sectional views shown in FIG. 25D. When the electromagnetic wave2504′ exits the waveguide device 2522 it may be transformed to a hybridwave mode such as, for example, an HE21 wave mode, an EH21 wave mode, ora hybrid wave mode with a different radial mode (e.g., HE2m or EH2m,where m>1).

FIGS. 25A-25D illustrate several embodiments for launching TM01, EH11,and other hybrid wave modes utilizing the waveguide device 2522 of FIG.25A. With an understanding of the electric field structures of otherwave modes that propagate on a coaxial cable (e.g., TM12, TM22, and soon), the MMICs 2524′ can be further configured in other ways to launchother wave modes (e.g., EH12, HE22, etc.) that have a low intensityz-field component and phi-field component in the electric fieldstructures near the outer surface of a transmission medium 2542, whichis useful for mitigating propagation losses due to a substance such aswater, droplets or other substances that can cause an attenuation of theelectric fields of an electromagnetic wave propagating along the outersurface of the transmission medium 2542.

FIG. 26 illustrates a flow diagram of an example, non-limitingembodiment of a method 2560 for sending and receiving electromagneticwaves. Method 2560 can be applied to waveguides 2522 of FIGS. 23A-23C,24 and 25A and/or other waveguide systems or launchers described andshown in the figures of the subject disclosure (e.g., FIGS. 7-14,18D-18K, 22A-22B and other drawings) for purposes of launching orreceiving substantially orthogonal wave modes such as those shown inFIG. 27. FIG. 27 depicts three cross-sectional views of an insulatedconductor where a TM00 fundamental wave mode, an HE11 wave mode withhorizontal polarization, and an HE11 wave mode with verticalpolarization, propagates respectively. The electric field structureshown in FIG. 27 can vary over time and is therefore an illustrativerepresentation at a certain instance or snapshot in time. The wave modesshown in FIG. 27 are orthogonal to each other. That is, a dot product ofcorresponding electric field vectors between any pair of the wave modesat each point of space and time produces a summation of zero. Thisproperty enables the TM00 wave mode, the HE11 wave mode with horizontalpolarization, and the HE11 wave mode with vertical polarization topropagate simultaneously along a surface of the same transmission mediumin the same frequency band without signal interference.

With this in mind, method 2560 can begin at step 2562 where a waveguidesystem of the subject disclosure can be adapted to receive communicationsignals from a source (e.g., a base station, a wireless signaltransmitted by a mobile or stationary device to an antenna of thewaveguide system as described in the subject disclosure, or by way ofanother communication source.). The communication signals can be, forexample, communication signals modulated according to a specificsignaling protocol (e.g., LTE, 5G, DOCSIS, DSL, etc.) operating in anative frequency band (e.g., 900 MHz, 1.9 GHz, 2.4 GHz, 5 GHz, etc.),baseband signals, analog signals, other signals, or any combinationsthereof. At step 2564, the waveguide system can be adapted to generateor launch on a transmission medium a plurality of electromagnetic wavesaccording to the communication signals by up-converting (or in someinstances down-converting) such communication signals to one or moreoperating frequencies of the plurality of electromagnetic waves. Thetransmission medium can be an insulated conductor as shown in FIG. 28,or an uninsulated conductor that is subject to environmental exposure tooxidation (or other chemical reaction based on environmental exposure)as shown in FIGS. 29 and 30. In other embodiments, the transmissionmedium can be a dielectric material such as a dielectric core describedin FIG. 18A.

To avoid interference, the waveguide system can be adapted tosimultaneously launch at step 2564 a first electromagnetic wave using aTM00 wave mode, a second electromagnetic wave using an HE11 wave modewith horizontal polarization, and a third electromagnetic wave using anHE11 wave mode with vertical polarization—see FIG. 27. Since the first,second and third electromagnetic waves are orthogonal (i.e.,non-interfering) they can be launched in the same frequency band withoutinterference or with a small amount of acceptable interference. Thecombined transmission of three orthogonal electromagnetic wave modes inthe same frequency band constitutes a form of wave mode divisionmultiplexing, which provides a means for increasing the informationbandwidth by a factor of three. By combining the principles of frequencydivision multiplexing with wave mode division multiplexing, bandwidthcan be further increased by configuring the waveguide system to launch afourth electromagnetic wave using a TM00 wave mode, a fifthelectromagnetic wave using an HE11 wave mode with horizontalpolarization, and a sixth electromagnetic wave using an HE11 wave modewith vertical polarization in a second frequency band that does notoverlap with the first frequency band of the first, second and thirdorthogonal electromagnetic waves. It will be appreciated that othertypes of multiplexing could be additionally or alternatively used withwave mode division multiplexing without departing from exampleembodiments.

To illustrate this point, suppose each of three orthogonalelectromagnetic waves in a first frequency band supports 1 GHz oftransmission bandwidth. And further suppose each of three orthogonalelectromagnetic waves in a second frequency band also supports 1 GHz oftransmission bandwidth. With three wave modes operating in two frequencybands, 6 GHz of information bandwidth is possible for conveyingcommunication signals by way of electromagnetic surface waves utilizingthese wave modes. With more frequency bands, the bandwidth can beincreased further.

Now suppose a transmission medium in the form of an insulated conductor(see FIG. 28) is used for surface wave transmissions. Further supposethe transmission medium has a dielectric layer with thicknessproportional to the conductor radius (e.g., a conductor having a 4 mmradius and an insulation layer with a 4 mm thickness). With this type oftransmission medium, the waveguide system can be configured to selectfrom several options for transmitting electromagnetic waves. Forexample, the waveguide system can be configured at step 2564 to transmitfirst through third electromagnetic waves using wave mode divisionmultiplexing at a first frequency band (e.g., at 1 GHz), third throughfourth electromagnetic waves using wave mode division multiplexing at asecond frequency band (e.g., at 2.1 GHz), seventh through ninthelectromagnetic waves using wave mode division multiplexing at a thirdfrequency band (e.g., at 3.2 GHz), and so on. Assuming eachelectromagnetic wave supports 1 GHz of bandwidth, collectively the firstthrough ninth electromagnetic waves can support 9 GHz of bandwidth.

Alternatively, or contemporaneous with transmitting electromagneticwaves with orthogonal wave modes at step 2564, the waveguide system canbe configured at step 2564 to transmit on the insulated conductor one ormore high frequency electromagnetic waves (e.g., millimeter waves). Inone embodiment, the one or more high frequency electromagnetic waves canbe configured in non-overlapping frequencies bands according to one ormore corresponding wave modes that are less susceptible to a water filmsuch as a TM0m wave mode and EH1m wave mode (where m>0), or an HE2m wavemode (where m>1) as previously described. In other embodiments, thewaveguide system can instead be configured to transmit one or more highfrequency electromagnetic waves in non-overlapping frequency bandsaccording to one or more corresponding wave modes that have longitudinaland/or azimuthal fields near the surface of the transmission medium thatmay be susceptible to water, but nonetheless exhibit low propagationlosses when the transmission medium is dry. A waveguide system can thusbe configured to transmit several combinations of wave modes on aninsulated conductor (as well as a dielectric-only transmission mediumsuch as a dielectric core) when the insulated conductor is dry.

Now suppose a transmission medium in the form of an uninsulatedconductor (see FIGS. 29-30) is used for surface wave transmissions.Further consider that the uninsulated conductor or bare conductor isexposed to an environment subject to various levels of moisture and/orrain (as well as air and atmospheric gases like oxygen). Uninsulatedconductors, such as overhead power lines and other uninsulated wires,are often made of aluminum which is sometimes reinforced with steel.Aluminum can react spontaneously with water and/or air to form aluminumoxide. An aluminum oxide layer can be thin (e.g., nano to micrometers inthickness). An aluminum oxide layer has dielectric properties and cantherefore serve as a dielectric layer. Accordingly, uninsulatedconductors can propagate not only TM00 wave modes, but also other wavemodes such as an HE11 wave mode with horizontal polarization, and anHE11 wave mode with vertical polarization at high frequencies based atleast in part on the thickness of the oxide layer. Accordingly,uninsulated conductors having an environmentally formed dielectric layersuch as an oxide layer can be used for transmitting electromagneticwaves using wave mode division multiplexing and frequency divisionmultiplexing. Other electromagnetic waves having a wave mode (with orwithout a cutoff frequency) that can propagate on an oxide layer arecontemplated by the subject disclosure and can be applied to theembodiments described in the subject disclosure.

In one embodiment, the term “environmentally formed dielectric layer”can represent an uninsulated conductor that is exposed to an environmentthat is not artificially created in a laboratory or other controlledsetting (e.g., bare conductor exposed to air, humidity, rain, etc. on autility pole or other exposed environment). In other embodiments, anenvironmentally formed dielectric layer can be formed in a controlledsetting such as a manufacturing facility that exposes uninsulatedconductors to a controlled environment (e.g., controlled humidity, orother gaseous substance) that forms a dielectric layer on the outersurface of the uninsulated conductor. In yet another alternativeembodiment, the uninsulated conductor can also be “doped” withparticular substances/compounds (e.g., a reactant) that facilitatechemical reactions with other substances/compounds that are eitheravailable in a natural environment or in an artificially createdlaboratory or controlled setting, thereby resulting in the creation ofthe environmentally formed dielectric layer.

Wave mode division multiplexing and frequency division multiplexing canprove useful in mitigating obstructions such as water accumulating on anouter surface of a transmission medium. To determine if mitigating anobstruction is necessary, a waveguide system can be configured at step2566 to determine if an obstruction is present on the transmissionmedium. A film of water (or water droplets) collected on an outersurface of the transmission medium due to rain, condensation, and/orexcess humidity can be one form of an obstruction that can causepropagation losses in electromagnetic waves if not mitigated. A splicingof a transmission medium or other object coupled to the outer surface ofthe transmission medium can also serve as an obstruction.

Obstructions can be detected by a source waveguide system that transmitselectromagnetic waves on a transmission medium and measures reflectedelectromagnetic waves based on these transmissions. Alternatively, or incombination, the source waveguide system can detect obstructions byreceiving communication signals (wireless or electromagnetic waves) froma recipient waveguide system that receives and performs quality metricson electromagnetic waves transmitted by the source waveguide system.When an obstruction is detected at step 2566, the waveguide system canbe configured to identify options to update, modify, or otherwise changethe electromagnetic waves being transmitted.

Suppose, for example, that in the case of an insulated conductor, thewaveguide system had launched at step 2564 a high order wave mode suchas TM01 wave mode with a frequency band that starts at 30 GHz having alarge bandwidth (e.g., 10 GHz) when the insulated conductor is dry. Forillustration purposes, a 10 GHz bandwidth will be assumed for anelectromagnetic wave having a TM01 wave mode.

Although it was noted earlier in the subject disclosure that a TM01 wavemode has a desirable electric field alignment that is not longitudinaland not azimuthal near the outer surface, it can nonetheless be subjectto some signal attenuation which in turn reduces its operating bandwidthwhen a water film (or droplets) accumulates on the insulated conductor.An electromagnetic wave having a TM01 wave mode with a bandwidth ofapproximately 10 GHz (30 to 40 GHz) on a dry insulated conductor candrop to a bandwidth of approximately 1 GHz (30 to 31 GHz) when theinsulated conductor is wet. To mitigate the loss in bandwidth, thewaveguide system can be configured to launch electromagnetic waves atmuch lower frequencies (e.g., less than 6 GHz) using wave mode divisionmultiplexing and frequency division multiplexing.

For example, the waveguide system can be configured to transmit a firstset of electromagnetic waves; specifically, a first electromagnetic wavehaving a TM00 wave mode, a second electromagnetic wave having an HE11wave mode with horizontal polarization, and a third electromagnetic wavehaving an HE11 wave mode with vertical polarization, eachelectromagnetic wave having a center frequency at 1 GHz. Assuming auseable frequency band from 500 MHz to 1.5 GHz to convey communicationsignals, each electromagnetic wave can provide 1 GHz of bandwidth, andcollectively 3 GHz of system bandwidth.

Suppose also the waveguide system is configured to transmit a second setof electromagnetic waves; specifically, a fourth electromagnetic wavehaving a TM00 wave mode, a fifth electromagnetic wave having an HE11wave mode with horizontal polarization, and a sixth electromagnetic wavehaving an HE11 wave mode with vertical polarization, eachelectromagnetic wave having a center frequency at 2.1 GHz. Assuming afrequency band from 1.6 GHz to 2.6 GHz, with a guard band of 100 MHzbetween the first and second sets of electromagnetic waves, eachelectromagnetic wave can provide 1 GHz of bandwidth, and collectively 3GHz of additional bandwidth, thereby now providing up to 6 GHz of systembandwidth.

Further suppose the waveguide system is also configured to transmit athird set of electromagnetic waves; specifically, a seventhelectromagnetic wave having a TM00 wave mode, an eighth electromagneticwave having an HE11 wave mode with horizontal polarization, and a ninthelectromagnetic wave having an HE11 wave mode with verticalpolarization, each electromagnetic wave having a center frequency at 3.2GHz. Assuming a frequency band from 2.7 GHz to 3.7 GHz, with a guardband of 100 MHz between the second and third sets of electromagneticwaves, each electromagnetic wave can provide 1 GHz of bandwidth, andcollectively 3 GHz of additional bandwidth, thereby now providing up to9 GHz of system bandwidth.

The combination of the TM01 wave mode, and the three sets ofelectromagnetic waves configured for wave mode division multiplexing andfrequency division multiplexing, provide a total system bandwidth of 10GHz, thereby restoring a bandwidth of 10 GHz previously available whenthe high frequency electromagnetic wave having the TM01 wave mode waspropagating on a dry insulated conductor. FIG. 31 illustrates a processfor performing mitigation of a TM01 wave mode subject to an obstructionsuch as a water film. FIG. 31 illustrates a transition from a dryinsulated conductor that supports a high bandwidth TM01 wave mode to awet insulated conductor that supports a lower bandwidth TM01 wave modethat is combined with low frequency TM00 and HE11 wave modes configuredaccording to wave mode division multiplexing (WMDM) and frequencydivision multiplexing (FDM) schemes to restore losses in systembandwidth.

Consider now an uninsulated conductor where the waveguide system hadlaunched at step 2564 a TM00 wave mode with a frequency band that startsat 10 GHz having a large bandwidth (e.g., 10 GHz). Suppose now thattransmission medium propagating the 10 GHz TM00 wave mode is exposed toan obstruction such as water. As noted earlier, a high frequency TM00wave mode on an insulated conductor is subject to a substantial amountof signal attenuation (e.g., 45 dB/M at 10 GHz) when a water film (ordroplets) accumulates on the outer surface of the insulated conductor.Similar attenuations will be present for a 10 GHz (or greater) TM00 wavemode propagating on an “uninsulated” conductor. An environmentallyexposed uninsulated conductor (e.g., aluminum), however, can have anoxide layer formed on the outer surface which can serve as a dielectriclayer that supports wave modes other than TM00 (e.g., HE11 wave modes).It is further noted that at lower frequencies a TM00 wave modepropagating on an insulated conductor exhibits a much lower attenuation(e.g., 0.62 dB/M at 4 GHz). A TM00 wave mode operating at less than 6GHz would similarly exhibit low propagation losses on an uninsulatedconductor. Accordingly, to mitigate the loss in bandwidth, the waveguidesystem can be configured to launch electromagnetic waves having a TM00wave mode at lower frequencies (e.g., 6 GHz or less) and electromagneticwaves having an HE11 wave mode configured for WMDM and FDM at higherfrequencies.

Referring back to FIG. 26, suppose then that the waveguide systemdetects an obstruction such as water at step 2566 on an environmentallyexposed uninsulated conductor. A waveguide system can be configured tomitigate the obstruction by transmitting a first electromagnetic waveconfigured with a TM00 wave mode having a center frequency at 2.75 GHz.Assuming a useable frequency band from 500 MHz to 5.5 GHz to conveycommunication signals, the electromagnetic waves can provide 5 GHz ofsystem bandwidth.

FIG. 32 illustrates a process for performing mitigation of a highfrequency TM00 wave mode subject to an obstruction such as a water filmdetected at step 2566. FIG. 31 illustrates a transition from a dryuninsulated conductor that supports a high bandwidth TM00 wave mode to awet uninsulated conductor that combines a low frequency TM00 wave modeand high frequency HE11 wave modes configured according to WMDM and FDMschemes to restore losses in system bandwidth.

It will be appreciated that the aforementioned mitigation techniques arenon-limiting. For example, the center frequencies described above candiffer between systems. Additionally, the original wave mode used beforean obstruction is detected can differ from the illustrations above. Forexample, in the case of an insulated conductor an EH11 wave mode can beused singly or in combination with a TM01 wave mode. It is alsoappreciated that WMDM and FDM techniques can be used to transmitelectromagnetic waves at all times and not just when an obstruction isdetected at step 2566. It is further appreciated that other wave modesthat can support WMDM and/or FDM techniques can be applied to and/orcombined with the embodiments described in the subject disclosure, andare therefore contemplated by the subject disclosure.

Referring back to FIG. 26, once a mitigation scheme using WMDM and/orFDM has been determined in accordance with the above illustrations, thewaveguide system can be configured at step 2568 to notify one or moreother waveguide systems of the mitigation scheme intended to be used forupdating one or more electromagnetic waves prior to executing the updateat step 2570. The notification can be sent wirelessly to one or moreother waveguide systems utilizing antennas if signal degradation in theelectromagnetic waves is too severe. If signal attenuation is tolerable,then the notification can be sent via the affected electromagneticwaves. In other embodiments, the waveguide system can be configured toskip step 2568 and perform the mitigation scheme using WMDM and/or FDMat step 2570 without notification. This embodiment can be applied incases where, for example, other recipient waveguide system(s) knowbeforehand what kind of mitigation scheme would be used, or therecipient waveguide system(s) are configured to use signal detectiontechniques to discover the mitigation scheme. Once the mitigation schemeusing WMDM and/or FDM has been initiated at step 2570, the waveguidesystem can continue to process received communication signals at steps2562 and 2564 as described earlier using the updated configuration ofthe electromagnetic waves.

At step 2566, the waveguide system can monitor if the obstruction isstill present. This determination can be performed by sending testsignals (e.g., electromagnetic surface waves in the original wave mode)to other waveguide system(s) and awaiting test results back from thewaveguide systems if the situation has improved, and/or by using otherobstruction detection techniques such as signal reflection testing basedon the sent test signals. Once the obstruction is determined to havebeen removed (e.g., the transmission medium becomes dry), the waveguidesystem can proceed to step 2572 and determine that a signal update wasperformed at step 2568 using WMDM and/or FDM as a mitigation technique.The waveguide system can then be configured to notify recipientwaveguide system(s) at step 2568 of the intent to restore transmissionsto the original wave mode, or bypass this step and proceed to step 2570where it restores transmissions to an original wave mode and assumes therecipient waveguide system(s) know the original wave modes andcorresponding transmission parameters, or can otherwise detect thischange.

A waveguide system can also be adapted to receive electromagnetic wavesconfigured for WMDM and/or FDM. For example, suppose that anelectromagnetic wave having a high bandwidth (e.g., 10 GHz) TM01 wavemode is propagating on an insulated conductor as shown in FIG. 31 andthat the electromagnetic wave is generated by a source waveguide system.At step 2582, a recipient waveguide system can be configured to processthe single electromagnetic wave with the TM01 wave mode under normalcondition. Suppose, however, that the source waveguide systemtransitions to transmitting electromagnetic waves using WMDM and FDMalong with a TM01 wave mode with a lower bandwidth on the insulatedconductor, as previously described in FIG. 31. In this instance, therecipient waveguide system would have to process multipleelectromagnetic waves of different wave modes. Specifically, therecipient waveguide system would be configured at step 2582 toselectively process each of the first through ninth electromagneticwaves using WMDM and FDM and the electromagnetic wave using the TM01wave mode as shown in FIG. 31.

Once the one or more electromagnetic waves have been received at step2582, the recipient waveguide can be configured to use signal processingtechniques to obtain the communication signals that were conveyed by theelectromagnetic wave(s) generated by the source waveguide system at step2564 (and/or step 2570 if an update has occurred). At step 2586, therecipient waveguide system can also determine if the source waveguidesystem has updated the transmission scheme. The update can be detectedfrom data provided in the electromagnetic waves transmitted by thesource waveguide system, or from wireless signals transmitted by thesource waveguide system. If there are no updates, the recipientwaveguide system can continue to receive and process electromagneticwaves at steps 2582 and 2584 as described before. If, however, an updateis detected at step 2586, the recipient waveguide system can proceed tostep 2588 to coordinate the update with the source waveguide system andthereafter receive and process updated electromagnetic waves at steps2582 and 2584 as described before.

It will be appreciated that method 2560 can be used in any communicationscheme including simplex and duplex communications between waveguidesystems. Accordingly, a source waveguide system that performs an updatefor transmitting electromagnetic waves according to other wave modeswill in turn cause a recipient waveguide system to perform similar stepsfor return electromagnetic wave transmissions. It will also beappreciated that the aforementioned embodiments associated with method2560 of FIG. 26 and the embodiments shown in FIGS. 27 through 32 can becombined in whole or in part with other embodiments of the subjectdisclosure for purposes of mitigating propagation losses caused by anobstruction at or in a vicinity of an outer surface of a transmissionmedium (e.g., insulated conductor, uninsulated conductor, or anytransmission medium having an external dielectric layer). Theobstruction can be a liquid (e.g., water), a solid object disposed onthe outer surface of the transmission medium (e.g., ice, snow, a splice,a tree limb, etc.), or any other objects located at or near the outersurface of the transmission medium.

While for purposes of simplicity of explanation, the respectiveprocesses are shown and described as a series of blocks in FIG. 26, itis to be understood and appreciated that the claimed subject matter isnot limited by the order of the blocks, as some blocks may occur indifferent orders and/or concurrently with other blocks from what isdepicted and described herein. Moreover, not all illustrated blocks maybe required to implement the methods described herein.

Referring now to FIGS. 33 and 34, block diagrams illustrating example,non-limiting embodiments for transmitting orthogonal wave modesaccording to the method 2560 of FIG. 26 are shown. FIG. 33 depicts anembodiment for simultaneously transmitting a TM00 wave mode, an HE11wave mode with vertical polarization, and an HE11 wave mode withhorizontal polarization as depicted in an instance in time in FIG. 27.In one embodiment, these orthogonal wave modes can be transmitted with awaveguide launcher having eight (8) MMICs as shown in FIG. 18K locatedat symmetrical locations (e.g., north, northeast, east, southeast,south, southwest, west, and northwest). The waveguide launcher of FIG.(or FIG. 18J) can also be configured with these 8 MMICs. Additionally,the waveguide launcher can be configured with a cylindrical sleeve 2523Aand tapered dielectric that wraps around the transmission medium (e.g.,insulated conductor, uninsulated conductor, or other cable with adielectric layer such as dielectric core). The housing assembly of thewaveguide launcher (not shown) can be configured to include a mechanism(e.g., a hinge) to enable a longitudinal opening of the waveguidelauncher for placement and latching around a circumference of atransmission medium.

With these configurations in mind, the waveguide launcher can includethree transmitters (TX1, TX2, and TX3) coupled to MMICs having variouscoordinate positions (see FIG. 25AG and FIG. 18W). The interconnectivitybetween the transmitters (TX1, TX2, and TX3) and the MMICs can beimplemented with a common printed circuit board or other suitableinterconnecting technology. The first transmitter (TX1) can beconfigured to launch a TM00 wave mode, the second transmitter (TX2) canbe configured to launch an HE11 vertical polarization wave mode, and thethird transmitter (TX3) can be configured to launch an HE11 horizontalpolarization wave mode.

A first signal port (shown as “SP1”) of the first transmitter (TX1) canbe coupled in parallel to each of the 8 MMICs. A second signal port(shown as “SP2”) of the first transmitter (TX1) can be coupled to aconductive sleeve 2523A that is placed on the transmission medium by thewaveguide launcher as noted above. The first transmitter (TX1) can beconfigured to receive a first group of the communication signalsdescribed in step 2562 of FIG. 26. The first group of communicationsignals can be frequency-shifted by the first transmitter (TX1) fromtheir native frequencies (if necessary) for an orderly placement of thecommunication signals in channels of a first electromagnetic waveconfigured according to the TM00 wave mode. The 8 MMICs coupled to thefirst transmitter (TX1) can be configured to up-convert (ordown-convert) the first group of the communication signals to the samecenter frequency (e.g., 1 GHz for the first electromagnetic wave asdescribed in relation to FIG. 31). All 8 MMICs would have synchronizedreference oscillators that can be phase locked using varioussynchronization techniques.

Since the 8 MMICs receive signals from the first signal port of thefirst transmitter (TX1) based on the reference provided by the secondsignal port, the 8 MMICs thereby receive signals with the same polarity.Consequently, once these signals have been up-converted (ordown-converted) and processed for transmission by the 8 MMICs, one ormore antennas of each of the 8 MMICs simultaneously radiates signalswith electric fields of the same polarity. Collectively, MMICs that areopposite in location to each other (e.g., MMIC north and MMIC south)will have an electric field structure aligned towards or away from thetransmission medium, thereby creating at a certain instance in time anoutward field structure like the TM00 wave mode shown in FIG. 27. Due tothe constant oscillatory nature of the signals radiated by the 8 MMICs,it will be appreciated that at other instances in time, the fieldstructure shown in FIG. 27 will radiate inward. By symmetricallyradiating electric fields with the same polarity the collection ofopposing MMICs contribute to the inducement of a first electromagneticwave having a TM00 wave mode that propagates on a transmission mediumwith a dielectric layer and can convey the first group of thecommunication signals to a receiving waveguide system.

Turning now to the second transmitter (TX2) in FIG. 33, this transmitterhas a first signal port (SP1) coupled to MMICs located in north,northeast and northwest positions, while a second signal port (SP2) ofthe second transmitter (TX2) is coupled to the MMICs located in south,southeast and southwest positions (see FIG. 18K). The second transmitter(TX2) can be configured to receive a second group of the communicationsignals described in step 2562 of FIG. 26, which differs from the firstgroup of the communication signals received by the first transmitter(TX1). The second group of communication signals can befrequency-shifted by the second transmitter (TX2) from their nativefrequencies (if necessary) for an orderly placement of the communicationsignals in channels of a second electromagnetic wave configuredaccording to an HE11 wave mode with vertical polarization. The 6 MMICscoupled to the second transmitter (TX2) can be configured to up-convert(or down-conversion) the second group of the communication signals tothe same center frequency as used for the TM00 wave mode (i.e., 1 GHz asdescribed in relation to FIG. 31). Since a TM00 wave mode is orthogonalto an HE11 wave mode with vertical polarization, they can share the samecenter frequency in an overlapping frequency band without interference.

Referring back to FIG. 33, the first signal port (SP1) of the secondtransmitter (TX2) generates signals of opposite polarity to the signalsof the second signal port (SP2). As a result, the electric fieldalignment of signals generated by one or more antennas of the northernMMIC will be of opposite polarity to the electric field alignment ofsignals generated by one or more antennas of the southern MMIC.Consequently, the electric fields of the north and south MMICs will havean electric field structure that is vertically aligned in the samedirection, thereby creating at a certain instance in time a northernfield structure like the HE11 wave mode with vertical polarization shownin FIG. 27. Due to the constant oscillatory nature of the signalsradiated by the north and south MMICs, it will be appreciated that atother instances in time, the HE11 wave mode will have a southern fieldstructure. Similarly, based on the opposite polarity of signals suppliedto the northeast and southeast MMICs by the first and second signalports, respectively, these MMICs will generate at a certain instance intime the curved electric field structure shown on the east side of theHE11 wave mode with vertical polarization depicted in FIG. 27. Also,based on the opposite polarity of signals supplied to the northwest andsouthwest MMICs, these MMICs will generate at a certain instance in timethe curved electric field structure shown on the west side of the HE11wave mode with vertical polarization depicted in FIG. 27.

By radiating electric fields with opposite polarity by opposing MMICs(north, northeast and northwest versus south, southeast and southwest),the collection of signals with a directionally aligned field structurecontribute to the inducement of a second electromagnetic wave having theHE11 wave mode with vertical polarization shown in FIG. 27. The secondelectromagnetic wave propagates along the “same” transmission medium aspreviously described for the first transmitter (TX1). Given theorthogonality of a TM00 wave mode and an HE11 wave mode with verticalpolarization, there will be ideally no interference between the firstelectromagnetic wave and the second electromagnetic wave. Consequently,the first and second electromagnetic waves having overlapping frequencybands propagating along the same transmission medium can successfullyconvey the first and second groups of the communication signals to thesame (or other) receiving waveguide system.

Turning now to the third transmitter (TX3) in FIG. 33, this transmitterhas a first signal port (SP1) coupled to MMICs located in east,northeast and southeast positions, while a second signal port (SP2) ofthe third transmitter (TX3) is coupled to the MMICs located in west,northwest and southwest positions (see FIG. 18K). The third transmitter(TX3) can be configured to receive a third group of the communicationsignals described in step 2562 of FIG. 26, which differs from the firstand second groups of the communication signals received by the firsttransmitter (TX1) and the second transmitter (TX2), respectively. Thethird group of communication signals can be frequency-shifted by thethird transmitter (TX3) from their native frequencies (if necessary) foran orderly placement of the communication signals in channels of asecond electromagnetic wave configured according to an HE11 wave modewith horizontal polarization. The 6 MMICs coupled to the thirdtransmitter (TX3) can be configured to up-convert (or down-conversion)the third group of the communication signals to the same centerfrequency as used for the TM00 wave mode and HE11 wave mode withvertical polarization (i.e., 1 GHz as described in relation to FIG. 31).Since a TM00 wave mode, an HE11 wave mode with vertical polarization,and an HE11 wave mode with horizontal polarization are orthogonal, theycan share the same center frequency in an overlapping frequency bandwithout interference.

Referring back to FIG. 33, the first signal port (SP1) of the thirdtransmitter (TX3) generates signals of opposite polarity to the signalsof the second signal port (SP2). As a result, the electric fieldalignment of signals generated by one or more antennas of the easternMMIC will be of opposite polarity to the electric field alignment ofsignals generated by one or more antennas of the western MMIC.Consequently, the electric fields of the east and west MMICs will havean electric field structure that is horizontally aligned in the samedirection, thereby creating at a certain instance in time a westernfield structure like the HE11 wave mode with horizontal polarizationshown in FIG. 27. Due to the constant oscillatory nature of the signalsradiated by the east and west MMICs, it will be appreciated that atother instances in time, the HE11 wave mode will have an eastern fieldstructure. Similarly, based on the opposite polarity of signals suppliedto the northeast and northwest MMICs by the first and second signalports, respectively, these MMICs will generate at a certain instance intime the curved electric field structure shown on the north side of theHE11 wave mode with horizontal polarization depicted in FIG. 27. Also,based on the opposite polarity of signals supplied to the southeast andsouthwest MMICs, these MMICs will generate at a certain instance in timethe curved electric field structure shown on the south side of the HE11wave mode with horizontal polarization depicted in FIG. 27.

By radiating electric fields with opposite polarity by opposing MMICs(east, northeast and southeast versus west, northwest and southwest),the collection of signals with a directionally aligned field structurecontribute to the inducement of a third electromagnetic wave having theHE11 wave mode with horizontal polarization shown in FIG. 27. The thirdelectromagnetic wave propagates along the “same” transmission medium aspreviously described for the first transmitter (TX1) and the secondtransmitter (TX2). Given the orthogonality of a TM00 wave mode, an HE11wave mode with vertical polarization, and an HE11 wave mode withhorizontal polarization, there will be, ideally, no interference betweenthe first electromagnetic wave, the second electromagnetic wave, and thethird electromagnetic wave. Consequently, the first, second and thirdelectromagnetic waves having overlapping frequency bands propagatingalong the same transmission medium can successfully convey the first,second and third groups of the communication signal to the same (orother) receiving waveguide system.

Because of the orthogonality of the electromagnetic waves describedabove, a recipient waveguide system can be configured to selectivelyretrieve the first electromagnetic wave having the TM00 wave mode, thesecond electromagnetic wave having the HE11 wave mode with verticalpolarization, and the third electromagnetic wave having the HE11 wavemode with horizontal polarization. After processing each of theseelectromagnetic waves, the recipient waveguide system can be furtherconfigured to obtain the first, second and third group of thecommunication signals conveyed by these waves. FIG. 34 illustrates ablock diagram for selectively receiving each of the first, second andthird electromagnetic waves.

Specifically, the first electromagnetic wave having the TM00 wave modecan be selectively received by a first receiver (RX1) shown in FIG. 34by taking the difference between the signals received by all 8 MMICs andthe signal reference provided by the metal sleeve 2523A as depicted inthe block diagram in FIG. 35. The second electromagnetic wave having theHE11 wave mode with vertical polarization can be selectively received bya second receiver (RX2) shown in FIG. 34 by taking the differencebetween the signals received by the MMICs located in north, northeastand northwest positions and the signals received by the MMICs located insouth, southeast and southwest positions as depicted in the blockdiagram in FIG. 36. The third electromagnetic wave having the HE11 wavemode with horizontal polarization can be selectively received by a thirdreceiver (RX3) shown in FIG. 34 by taking the difference between thesignals received by the MMICs located in east, northeast and southeastpositions and the signals received by the MMICs located in west,northwest and southwest positions as depicted in the block diagram inFIG. 37.

FIG. 38 illustrates a simplified functional block diagram of an MMIC.The MMIC can, for example, utilize a mixer coupled to a reference (TX)oscillator that shifts one of the communication signals supplied by oneof the signal ports (SP1 or SP2) of one of the transmitters (TX1, TX2 orTX3) to a desired center frequency in accordance with the configurationsshown in FIG. 33. For example, in the case of TX1, the communicationsignal from SP1 is supplied to a transmit path of each of the MMICs(i.e., NE, NW, SE, SW, N, S, E, and W). In the case of TX2, thecommunication signal from SP1 is supplied to another transmit path ofthree MMICs (i.e., N, E, and NW). Note the transmit paths used by MMICsN, E and W for the communication signal supplied by SP1 of TX2 aredifferent from the transmit paths used by the MMICs for thecommunication signal supplied by SP1 of TX1. Similarly, thecommunication signal from SP2 of TX2 is supplied to another transmitpath of three other MMICs (i.e., S, SE, and SW). Again, the transmitpaths used by MMICs S, SE and SW for the communication signal suppliedby SP2 of TX2 are different from the transmit paths used by the MMICsfor the communication signals from SP1 of TX1, and SP1 of TX2. Lastly,in the case of TX3, the communication signal from SP1 is supplied to yetanother transmit path of three MMICs (i.e., E, NE, and SE). Note thetransmit paths used for MMICs E, NE, and SE for the communication signalfrom SP1 of TX3 are different from the transmit paths used by the MMICsfor the communication signals supplied by SP1 of TX1, SP1 of TX2, andSP2 of TX2. Similarly, the communication signal from SP2 of TX3 issupplied to another transmit path of three other MMICs (i.e., W, NW, andSW). Again, the transmit paths used by MMICs W, NW, and SW for thecommunication signal supplied by SP2 of TX3 are different from thetransmit paths used by the MMICs for the communication signals from SP1of TX1, SP1 of TX2, and SP2 of TX2, and SP1 of TX3.

Once the communication signals have been frequency-shifted by the mixershown in the transmit path, he frequency-shifted signal generated by themixer can then be filtered by a bandpass filter that removes spurioussignals. The output of the bandpass filter in turn can be provided to apower amplifier that couples to an antenna by way of a duplexer forradiating signals in the manner previously described. The duplexer canbe used to isolate a transmit path from a receive path. The illustrationof FIG. 38 is intentionally oversimplified to enable ease ofillustration.

It will be appreciated that other components (not shown) such as animpedance matching circuit, phase lock loop, or other suitablecomponents for improving the accuracy and efficiency of the transmissionpath (and receive path) is contemplated by the subject disclosure.Furthermore, while a single antenna can be implemented by each MMIC,other designs with multiple antennas can likewise be employed. It isfurther appreciated that to achieve more than one orthogonal wave modewith overlapping frequency bands (e.g., TM00, HE11 Vertical, and HE11Horizontal wave modes described above), the transmit path can berepeated N times using the same reference oscillator. N can represent aninteger associated with the number of instances the MMIC is used togenerate each of the wave modes. For example, in FIG. 33, MMIC NE isused three times; hence, MMIC NE has three transmit paths (N=3), MMIC NWis used three times; hence, MMIC NW has three transmit paths (N=3), MMICN is used twice; hence, MMIC N has two transmit paths (N=2), and so on.If frequency division multiplexing is employed to generate the same wavemodes in other frequency band(s) (see FIGS. 31 and 32), the transmitpath can be further repeated using different reference oscillator(s)that are centered at the other frequency band(s).

In the receive path shown in FIG. 38, N signals supplied by N antennasvia the duplexer of each transmit path in the MMIC can be filtered by acorresponding N bandpass filters, which supply their output to Nlow-noise amplifiers. The N low-noise amplifiers in turn supply theirsignals to N mixers to generate N intermediate-frequency receivedsignals. As before, N is representative of the number of instances theMMIC is used for receiving wireless signals for different wave modes.For example, in FIG. 34, MMIC NE is used in three instances; hence, MMICNE has three receive paths (N=3), MMIC N is used in two instances;hence, MMIC N has two receive paths (N=2), and so on.

Referring back to FIG. 38, to reconstruct a wave mode signal, Y receivedsignals supplied by receiver paths of certain MMICs or a reference froma metal sleeve is subtracted from X received signals supplied by otherMMICs based on the configurations shown in FIGS. 35-37. For example, aTM00 signal is reconstructed by supplying the received signals of allMMICs (NE, NW, SE, SW, N, S, E, W) to the plus port of the summer (i.e.,X signals), while the reference signal from the metal sleeve is suppliedto the negative port of the summer (i.e., Y signal)—see FIG. 35. Thedifference between the X and Y signals results in the TM00 signal. Toreconstruct the HE11 Vertical signal, the received signals of MMICs N,NE, and NW are supplied to the plus port of the summer (i.e., Xsignals), while the received signals of MMICs S, SE, and SW are suppliedto the negative port of the summer (i.e., Y signals)—see FIG. 36. Thedifference between the X and Y signals results in the HE11 verticalsignal. Lastly, to reconstruct the HE11 Horizontal signal, the receivedsignals of MMICs E, NE, and SE are supplied to the plus port of thesummer (i.e., X signals), while the received signals of MMICs W, NW, andSW are supplied to the negative port of the summer (i.e., Y signals)—seeFIG. 37. The difference between the X and Y signals results in the HE11horizontal signal. Since there are three wave mode signals beingreconstructed, the block diagram of the summer with the X and Y signalsis repeated three times.

Each of these reconstructed signals is at intermediate frequencies.These intermediate-frequency signals are provided to receivers (RX1, RX2and RX3) which include circuitry (e.g., a DSP, A/D converter, etc.) forprocessing and to selectively obtain communication signals therefrom.Similar to the transmit paths, the reference oscillators of the threereceiver paths can be configured to be synchronized with phase lock looptechnology or other suitable synchronization technique. If frequencydivision multiplexing is employed for the same wave modes in otherfrequency band(s) (see FIGS. 31 and 32), the receiver paths can befurther repeated using a different reference oscillator that is centeredat the other frequency band(s).

It will be appreciated that other suitable designs that can serve asalternative embodiments to those shown in FIGS. 33-38 can be used fortransmitting and receiving orthogonal wave modes. For example, there canbe fewer or more MMICs than described above. In place of the MMICs, orin combination, slotted launchers as shown in FIGS. 18D-18E, 18G, and18I can be used. It is further appreciated that more or fewersophisticated functional components can be used for transmitting orreceiving orthogonal wave modes. Accordingly, other suitable designsand/or functional components are contemplated by the subject disclosurefor transmitting and receiving orthogonal wave modes.

Referring now to FIG. 39, a block diagram illustrating an example,non-limiting embodiment of a polyrod antenna 2600 for transmittingwireless signals is shown. The polyrod antenna 2600 can be one of anumber of polyrod antennas that are utilized in an antenna array, suchas array 1976 of FIG. 19F. The antenna array can facilitate or otherwiseenable beam steering which can include beam forming. The beam steeringcan be associated with communication signals, including voice, video,data, messaging, testing signals.

In one or more embodiments, the polyrod antenna 2600 can include a core2628 having a number of different regions or portions. The core 2628 canbe connected with a waveguide 2622 configured to confine anelectromagnetic wave at least in part within the core (e.g., in a firstregion of the core covered by the waveguide). In one embodiment (notshown), the waveguide 2622 can have an opening for accepting atransmission medium (e.g., a dielectric cable) or other couplingdevices. In another embodiment, the waveguide 2622 can have a generator,radiating element or other components therein that generateelectromagnetic waves for propagating along the core 2628.

In one embodiment, another region 2606 of the core 2628 (e.g., outsideof the waveguide 2622) is configured to reduce a propagation loss of anelectromagnetic wave as the electromagnetic wave propagates into thatregion, such as by having a non-tapered or otherwise uniform diameter ofthe core. The particular length and/or diameter of the region 2606 ofthe core 2628 can be selected to facilitate the reduction of propagationloss of the electromagnetic wave.

In one embodiment, another region 2612 of the core 2628 (e.g., thedistal portion or end of the core that is outside of the waveguide 2622)can be tapered and can facilitate transmitting a wireless signal, suchas based on the electromagnetic wave propagating along the core 2628.The particular length, diameter, and/or angle of taper of the region2612 of the core 2628 can be selected to facilitate transmitting of thewireless signals. In one embodiment, the tip or end 2675 of the region2612 can be truncated (as shown in FIG. 39) or pointed.

In one embodiment, the length and/or diameter of the core 2628 can beselected based on a wavelength of the electromagnetic wave that will bepropagating along the dielectric core. For example, a diameter ofgreater than ¼λ can be used for the region 2606.

In one embodiment, an inner surface of the waveguide 2622 can beconstructed from a metallic material or other materials that reflectelectromagnetic waves and thereby enables the waveguide 2622 to beconfigured to guide the electromagnetic wave towards the core 2628. Inone embodiment, the core 2628 can comprise a dielectric core (e.g., asdescribed herein) that extends to, or in proximity of, the inner surfaceof the waveguide 2622. In another embodiment, the dielectric core can besurrounded by cladding (such as shown in FIG. 18A), whereby the claddingextends to the inner surface of the waveguide 2622. In yet otherembodiments, the core 2628 can comprise an insulated conductor, wherethe insulation extends to the inner surface of the waveguide 2622. Inthis embodiment, the insulated conductor can be a power line, a coaxialcable, or other types of insulated conductors. In one example, thetapered outer shape may extend to the diameter of the metallic wire. Inanother example, the tapered outer shape may extend to and includetapering of the metallic wire. In yet another example, the metallic wiremay or may not continue beyond the tip 2675.

Referring to FIG. 40, an e-field distribution is illustrated for thepolyrod antenna 2600. As shown, the electromagnetic wave is confined orsubstantially confined within the waveguide 2622 and then propagatesalong the core 2628 until it is transmitted as a wireless signal fromthe region 2612 of the core.

Referring now to FIGS. 41 and 42, diagrams are shown illustrating anexample, non-limiting embodiment of a polyrod antenna array 2900 whichutilizes four polyrod antennas 2600 for transmitting wireless signals.In this example, the polyrod antenna array 2900 utilizes the samepolyrod antennas 2600, which are uniformly spaced apart, such as 0.8 cmon center. The particular type of polyrod antenna, the number of polyrodantennas, and/or the spacing in the array can be selected according tovarious factors, such as based on parameters of the wireless signalsand/or electromagnetic waves that are being utilized.

Referring now to FIG. 43A, a block diagram illustrating an example,non-limiting embodiment of a hollow horn antenna 3600 is shown. In oneembodiment, the hollow horn antenna 3600 can be used in an array. As anexample, hollow horn antenna 3600 can be made from TEFLON and/or caninclude a cylindrical V-band feed 3622 for generating a signal to bewirelessly transmitted. FIG. 43B illustrates an e-field distribution forthe hollow horn antenna 3600. As shown, the electromagnetic waves areconfined or substantially confined within the cylinder 3622.

Turning now to FIG. 44A, a block diagram illustrating an example,non-limiting embodiment of a communication system 4400 in accordancewith various aspects of the subject disclosure is shown. Thecommunication system 4400 can include a macro base station 4402 such asa base station or access point having antennas that covers one or moresectors (e.g., 6 or more sectors). The macro base station 4402 can becommunicatively coupled to a communication node 4404A that serves as amaster or distribution node for other communication nodes 4404B-4404Edistributed at differing geographic locations inside or beyond acoverage area of the macro base station 4402. The communication nodes4404 operate as a distributed antenna system configured to handlecommunications traffic associated with client devices such as mobiledevices (e.g., cell phones) and/or fixed/stationary devices (e.g., acommunication device in a residence, or commercial establishment) thatare wirelessly coupled to any of the communication nodes 4404. Inparticular, the wireless resources of the macro base station 4402 can bemade available to mobile devices by allowing and/or redirecting certainmobile and/or stationary devices to utilize the wireless resources of acommunication node 4404 in a communication range of the mobile orstationary devices.

The communication nodes 4404A-4404E can be communicatively coupled toeach other over an interface 4410. In one embodiment, the interface 4410can comprise a wired or tethered interface (e.g., fiber optic cable). Inother embodiments, the interface 4410 can comprise a wireless RFinterface forming a radio distributed antenna system. In variousembodiments, the communication nodes 4404A-4404E can include one or moreantennas, such as dielectric horn antennas or antenna arrays, poly rodantennas or antenna arrays or any of the other antennas describedherein. The communication nodes 4404A-4404E can be configured to providecommunication services to mobile and stationary devices according toinstructions provided by the macro base station 4402. In other examplesof operation however, the communication nodes 4404A-4404E operate merelyas analog repeaters to spread the coverage of the macro base station4402 throughout the entire range of the individual communication nodes4404A-4404E.

The micro base stations (depicted as communication nodes 4404) candiffer from the macro base station in several ways. For example, thecommunication range of the micro base stations can be smaller than thecommunication range of the macro base station. Consequently, the powerconsumed by the micro base stations can be less than the power consumedby the macro base station. The macro base station optionally directs themicro base stations as to which mobile and/or stationary devices theyare to communicate with, and which carrier frequency, spectralsegment(s) and/or timeslot schedule of such spectral segment(s) are tobe used by the micro base stations when communicating with certainmobile or stationary devices. In these cases, control of the micro basestations by the macro base station can be performed in a master-slaveconfiguration or other suitable control configurations. Whetheroperating independently or under the control of the macro base station4402, the resources of the micro base stations can be simpler and lesscostly than the resources utilized by the macro base station 4402.

Turning now to FIG. 44B, a block diagram illustrating an example,non-limiting embodiment of the communication nodes 4404B-4404E of thecommunication system 4400 of FIG. 44A is shown. In this illustration,the communication nodes 4404B-4404E are placed on a utility fixture suchas a light post. In other embodiments, some of the communication nodes4404B-4404E can be placed on a building or a utility post or pole thatis used for distributing power and/or communication lines. Thecommunication nodes 4404B-4404E in these illustrations can be configuredto communicate with each other over the interface 4410, which in thisillustration is shown as a wireless interface. The communication nodes4404B-4404E can also be configured to communicate with mobile orstationary devices 4406A, 4406B, 4406C over a wireless interface 4411(e.g., 1.930 GHz in the case of 4406A, 1.935 GHz in the case of 4406B,1.940 GHz in the case of 4406C) that conforms to one or morecommunication protocols (e.g., fourth generation (4G) wireless signalssuch as LTE signals or other 4G signals, fifth generation (5G) wirelesssignals, WiMAX, 802.11 signals, ultra-wideband signals, etc.). Thecommunication nodes 4404 can be configured to exchange signals over theinterface 4410 at an operating frequency that is may be higher (e.g., 28GHz, 38 GHz, 60 GHz, 80 GHz or higher) than the operating frequency usedfor communicating with the mobile or stationary devices (e.g., 1.9 GHz)over interface 4411. The high carrier frequency and a wider bandwidthcan be used for communicating between the communication nodes 4404enabling the communication nodes 4404 to provide communication servicesto multiple mobile or stationary devices via one or more differingfrequency bands, (e.g. a 900 MHz band, 1.9 GHz band, a 2.4 GHz band,and/or a 5.8 GHz band, etc.) and/or one or more differing protocols. Inother embodiments, particularly where the interface 4410 is implementedvia a guided wave communications system on a wire, a wideband spectrumin a lower frequency range (e.g. in the range of 2-6 GHz, 4-10 GHz,etc.) can be employed.

Turning now to FIG. 44C, a block diagram illustrating an example,non-limiting embodiment of downlink (e.g., 30-110 GHz) and uplink (e.g.,30-110 GHz) communication techniques for enabling a base station tocommunicate with the communication nodes 4404 of FIG. 44A is shown. Inthe illustrations of FIG. 44C, downlink signals (i.e., signals directedfrom the macro base station 4402 to the communication nodes 4404) can bespectrally divided into control channels 4422, downlink spectralsegments 4426 each including modulated signals which can be frequencyconverted to their original/native frequency band (e.g., cellular band,or other native frequency band) for enabling the communication nodes4404 to communicate with one or more mobile or stationary devices 4426,and pilot signals 4424 which can be supplied with some or all of thespectral segments 4426 for mitigating distortion created between thecommunication nodes 4424. The pilot signals 4424 can be processed bytethered or wireless transceivers of downstream communication nodes 4404to remove distortion from a receive signal (e.g., phase distortion).Each downlink spectral segment 4426 can be allotted a bandwidth 4425sufficiently wide (e.g., 50 MHz) to include a corresponding pilot signal4424 and one or more downlink modulated signals located in frequencychannels (or frequency slots) in the spectral segment 4426. Themodulated signals can represent cellular channels, WLAN channels orother modulated communication signals (e.g., 10-20 MHz), which can beused by the communication nodes 4404 for communicating with one or moremobile or stationary devices 4406.

Uplink modulated signals generated by mobile or stationary communicationdevices in their native/original frequency bands (e.g., cellular band,or other native frequency band) can be frequency converted and therebylocated in frequency channels (or frequency slots) in the uplinkspectral segment 4430. The uplink modulated signals can representcellular channels, WLAN channels or other modulated communicationsignals. Each uplink spectral segment 4430 can be allotted a similar orsame bandwidth 4425 to include a pilot signal 4428 which can be providedwith some or each spectral segment 4430 to enable upstream communicationnodes 4404 and/or the macro base station 4402 to remove distortion(e.g., phase error).

In the embodiment shown, the downlink and uplink spectral segments 4426and 4430 each comprise a plurality of frequency channels (or frequencyslots), which can be occupied with modulated signals that have beenfrequency converted from any number of native/original frequency bands(e.g. a 900 MHz band, 1.9 GHz band, a 2.4 GHz band, and/or a 5.8 GHzband, etc.). The modulated signals can be up-converted to adjacentfrequency channels in downlink and uplink spectral segments 4426 and4430. In this fashion, while some adjacent frequency channels in adownlink spectral segment 4426 can include modulated signals originallyin a same native/original frequency band, other adjacent frequencychannels in the downlink spectral segment 4426 can also includemodulated signals originally in different native/original frequencybands, but frequency converted to be located in adjacent frequencychannels of the downlink spectral segment 4426. For example, a firstmodulated signal in a 1.9 GHz band and a second modulated signal in thesame frequency band (i.e., 1.9 GHz) can be frequency converted andthereby positioned in adjacent frequency channels of a downlink spectralsegment 4426. In another illustration, a first modulated signal in a 1.9GHz band and a second communication signal in a different frequency band(i.e., 2.4 GHz) can be frequency converted and thereby positioned inadjacent frequency channels of a downlink spectral segment 4426.Accordingly, frequency channels of a downlink spectral segment 4426 canbe occupied with any combination of modulated signals of the same ordiffering signaling protocols and of a same or differing native/originalfrequency bands.

Similarly, while some adjacent frequency channels in an uplink spectralsegment 4430 can include modulated signals originally in a samefrequency band, adjacent frequency channels in the uplink spectralsegment 4430 can also include modulated signals originally in differentnative/original frequency bands, but frequency converted to be locatedin adjacent frequency channels of an uplink segment 4430. For example, afirst communication signal in a 2.4 GHz band and a second communicationsignal in the same frequency band (i.e., 2.4 GHz) can be frequencyconverted and thereby positioned in adjacent frequency channels of anuplink spectral segment 4430. In another illustration, a firstcommunication signal in a 1.9 GHz band and a second communication signalin a different frequency band (i.e., 2.4 GHz) can be frequency convertedand thereby positioned in adjacent frequency channels of the uplinkspectral segment 4426. Accordingly, frequency channels of an uplinkspectral segment 4430 can be occupied with any combination of modulatedsignals of a same or differing signaling protocols and of a same ordiffering native/original frequency bands. It should be noted that adownlink spectral segment 4426 and an uplink spectral segment 4430 canthemselves be adjacent to one another and separated by only a guard bandor otherwise separated by a larger frequency spacing, depending on thespectral allocation in place.

Turning now to FIG. 44D, a graphical diagram 4460 illustrating anexample, non-limiting embodiment of a frequency spectrum is shown. Inparticular, a spectrum 4462 (see frequency on the horizontal axis) isshown for a distributed antenna system that conveys modulated signalsoccupying frequency channels of uplink or downlink spectral segmentsafter they have been converted in frequency (e.g. via up-conversion ordown-conversion) from one or more original/native spectral segments intothe spectrum 4462.

As previously discussed two or more different communication protocolscan be employed to communicate upstream and downstream data. When two ormore differing protocols are employed, a first subset of the downlinkfrequency channels of a downlink spectral segment 4426 can be occupiedby frequency converted modulated signals in accordance with a firststandard protocol and a second subset of the downlink frequency channelsof the same or a different downlink spectral segment 4430 can beoccupied by frequency converted modulated signals in accordance with asecond standard protocol that differs from the first standard protocol.Likewise a first subset of the uplink frequency channels of an uplinkspectral segment 4430 can be received by the system for demodulation inaccordance with the first standard protocol and a second subset of theuplink frequency channels of the same or a different uplink spectralsegment 4430 can be received in accordance with a second standardprotocol for demodulation in accordance with the second standardprotocol that differs from the first standard protocol.

In the example shown, the downstream channel band 4444 includes a firstplurality of downstream spectral segments represented by separatespectral shapes of a first type representing the use of a firstcommunication protocol. The downstream channel band 4444′ includes asecond plurality of downstream spectral segments represented by separatespectral shapes of a second type representing the use of a secondcommunication protocol. Likewise the upstream channel band 4446 includesa first plurality of upstream spectral segments represented by separatespectral shapes of the first type representing the use of the firstcommunication protocol. The upstream channel band 4446′ includes asecond plurality of upstream spectral segments represented by separatespectral shapes of the second type representing the use of the secondcommunication protocol. These separate spectral shapes are meant to beplaceholders for the frequency allocation of each individual spectralsegment along with associated reference signals, control channels and/orclock signals. While the individual channel bandwidth is shown as beingroughly the same for channels of the first and second type, it should benoted that upstream and downstream channel bands 4444, 4444′, 4446 and4446′ may be of differing bandwidths. Additionally, the spectralsegments in these channel bands of the first and second type may be ofdiffering bandwidths, depending on available spectrum and/or thecommunication standards employed.

Turning now to FIG. 44E, a graphical diagram 4470 illustrating anexample, non-limiting embodiment of a frequency spectrum is shown. Inparticular a portion of the spectrum 4462 of FIG. 44D is shown for adistributed antenna system that conveys modulated signals in the form ofchannel signals that have been converted in frequency (e.g. viaup-conversion or down-conversion) from one or more original/nativespectral segments.

The portion 4472 (see frequency on the horizontal axis) includes aportion of a downlink or uplink spectral segment 4426 and 4430 (channelsignal) that is represented by a spectral shape and that represents aportion of the bandwidth set aside for a control channel, referencesignal, and/or clock signal. The spectral shape 4474, for example,represents a control channel that is separate from reference signal 4479and a clock signal 4478. It should be noted that the clock signal 4478is shown with a spectral shape representing a sinusoidal signal that mayrequire conditioning into the form of a more traditional clock signal.In other embodiments however, a traditional clock signal could be sentas a modulated carrier wave such by modulating the reference signal 4479via amplitude modulation or other modulation technique that preservesthe phase of the carrier for use as a phase reference. In otherembodiments, the clock signal could be transmitted by modulating anothercarrier wave or as another signal. Further, it is noted that both theclock signal 4478 and the reference signal 4479 are shown as beingoutside the frequency band of the control channel 4474.

In another example, the portion 4475 (see frequency on the horizontalaxis) includes a portion of a downlink or uplink spectral segment 4426and 4430 (channel signal) that is represented by a portion of a spectralshape that represents a portion of the bandwidth set aside for a controlchannel, reference signal, and/or clock signal. The spectral shape 4476represents a control channel having instructions that include digitaldata that modulates the reference signal, via amplitude modulation,amplitude shift keying or other modulation technique that preserves thephase of the carrier for use as a phase reference. The clock signal 4478is shown as being outside the frequency band of the spectral shape 4476.The reference signal, being modulated by the control channelinstructions, is in effect a subcarrier of the control channel and isin-band to the control channel. Again, the clock signal 4478 is shownwith a spectral shape representing a sinusoidal signal, in otherembodiments however, a traditional clock signal could be sent as amodulated carrier wave or other signal. In this case, the instructionsof the control channel can be used to modulate the clock signal 4478instead of the reference signal.

Consider the following example, where the control channel 4476 iscarried via modulation of a reference signal in the form of a continuouswave (CW) from which the phase distortion in the receiver is correctedduring frequency conversion of the downlink or uplink spectral segment4426 and 4430 back to its original/native spectral segment. The controlchannel 4476 can be modulated with a robust modulation such as pulseamplitude modulation, binary phase shift keying, amplitude shift keyingor other modulation scheme to carry instructions between networkelements of the distributed antenna system such as network operations,administration and management traffic and other control data. In variousembodiments, the control data can include without limitation:

-   -   Status information that indicates online status, offline status,        and network performance parameters of each network element.    -   Network device information such as module names and addresses,        hardware and software versions, device capabilities, etc.    -   Spectral information such as frequency conversion factors,        channel spacing, guard bands, uplink/downlink allocations,        uplink and downlink channel selections, etc.    -   Environmental measurements such as weather conditions, image        data, power outage information, line of sight blockages, etc.

In a further example, the control channel data can be sent viaultra-wideband (UWB) signaling. The control channel data can betransmitted by generating radio energy at specific time intervals andoccupying a larger bandwidth, via pulse-position or time modulation, byencoding the polarity or amplitude of the UWB pulses and/or by usingorthogonal pulses. In particular, UWB pulses can be sent sporadically atrelatively low pulse rates to support time or position modulation, butcan also be sent at rates up to the inverse of the UWB pulse bandwidth.In this fashion, the control channel can be spread over an UWB spectrumwith relatively low power, and without interfering with CW transmissionsof the reference signal and/or clock signal that may occupy in-bandportions of the UWB spectrum of the control channel.

In one or more embodiments, communication device 4510 can include anantenna array 4515 for transmitting wireless signals. In one or moreembodiments, the antenna array 4515 can perform beam steering. Forexample, the antenna array 4515 can utilize a first subset of antennasof the antenna array to transmit first wireless signals 4525 directed(as shown by reference number 4527) via beam steering towards thecommunication device 4550. A second subset of antennas of the antennaarray 4515 can transmit second wireless signals 4530 directed (as shownby reference number 4532) via the beam steering towards a transmissionmedium 4575 (e.g., a power line connected between the utility poles4520, 4560). In one or more embodiments, the aforementioned beams can besimultaneously created by the same set of antennas in arrays 4510 and4550. In one or more embodiments, the beam steering can enable theantenna array to communicate with more than one wireless receiver withor without directing wireless signals to a transmission medium. In oneor more embodiments, the beam steering can enable the antenna array todirect the wireless signals to more than one transmission medium with orwithout communicating with a wireless receiver.

The first and second wireless signals 4525, 4530 can be associated withcommunication signals that are to be transmitted over the network. Forinstance, the first and second wireless signals 4525, 4530 can be thesame signals. In another example, the first wireless signals 4525 canrepresent a first subset of the communication signals, while the secondwireless signals 4530 represent a second subset of the communicationsignals. In one embodiment, the first and second wireless signals 4525,4530 can be different and can be based on interleaving of a group ofcommunication signals, such as video packets, and so forth. Thecommunication signals can be various types of signals includinginformation associated with subscriber services, network control,testing, and so forth.

In one or more embodiments, the second wireless signals 4530 induceelectromagnetic waves 4540. For example, the electromagnetic waves 4540are induced at a physical interface of the transmission medium 4575 andpropagate (as shown by reference number 4542) without requiring anelectrical return path. The electromagnetic waves 4540 are guided by thetransmission medium 4575 towards the communication device 4550, which ispositioned in proximity to the transmission medium. The electromagneticwaves 4540 can be representative of the second wireless signals 4530which are associated with the communication signals.

In one or more embodiments, the communication device 4550 can include areceiver that is configured to receive the electromagnetic waves 4540that are propagating along the transmission medium 4575. Various typesof receivers can be used for receiving the electromagnetic waves 4540,such as devices shown in FIGS. 7, 8 and 9A. System 4500 enables thecommunication device 4510 to transmit information which is received bythe communication device 4550 (e.g., another antenna array 4555) via thewireless communication path 4527 and via being guided by thetransmission medium 4575.

In one or more embodiments, the antenna arrays 4515, 4555 can includepolyrod antennas. For example, each of the polyrod antennas can includea core that is connected with a waveguide that is configured to confinean electromagnetic wave at least in part within the core in a particularregion of the core. In one embodiment, each of the polyrod antennas caninclude a core having a first region, a second region, a third region,and a fourth region, where the core comprises an interface in the firstregion. One of the plurality of transmitters can generate a firstelectromagnetic wave that induces a second electromagnetic wave at theinterface of the first region. The core can be connected with awaveguide that is configured to confine the second electromagnetic waveat least in part within the core in the first region, where the secondregion of the core is configured to reduce a radiation loss of thesecond electromagnetic wave as the second electromagnetic wavepropagates into the second region. The third region of the core can beconfigured to reduce a propagation loss of the second electromagneticwave as the second electromagnetic wave propagates into the thirdregion. The fourth region of the core can be outside of the waveguideand can be tapered to facilitate transmitting one of the first or secondwireless signals based on the second electromagnetic wave.

In one or more embodiments, the communication device 4510 can provide aphase adjustment to the second wireless signals 4530 to accomplish beamsteering towards the transmission medium 4575. FIG. 45 illustrates theantenna array 4555 and the receiver 4565 being co-located atcommunication device 4550, however, in another embodiment the antennaarray 4555 and the receiver 4565 can be separate devices that may or maynot be in proximity to each other. For example, the first wirelesssignals 4525 can be received by the antenna array 4555 of thecommunication device 4550 while the electromagnetic waves 4540 can bereceived by a receiver of a different communication device (not shown)that is in proximity to the transmission medium 4575.

Referring now to FIG. 46, there is illustrated a block diagram of acomputing environment in accordance with various aspects describedherein. In order to provide additional context for various embodimentsof the embodiments described herein, FIG. 46 and the followingdiscussion are intended to provide a brief, general description of asuitable computing environment 4600 in which the various embodiments ofthe subject disclosure can be implemented. While the embodiments havebeen described above in the general context of computer-executableinstructions that can run on one or more computers, those skilled in theart will recognize that the embodiments can be also implemented incombination with other program modules and/or as a combination ofhardware and software.

Generally, program modules comprise routines, programs, components, datastructures, etc., that perform particular tasks or implement particularabstract data types. Moreover, those skilled in the art will appreciatethat the inventive methods can be practiced with other computer systemconfigurations, comprising single-processor or multiprocessor computersystems, minicomputers, mainframe computers, as well as personalcomputers, hand-held computing devices, microprocessor-based orprogrammable consumer electronics, and the like, each of which can beoperatively coupled to one or more associated devices.

As used herein, a processing circuit includes processor as well as otherapplication specific circuits such as an application specific integratedcircuit, digital logic circuit, state machine, programmable gate arrayor other circuit that processes input signals or data and that producesoutput signals or data in response thereto. It should be noted thatwhile any functions and features described herein in association withthe operation of a processor could likewise be performed by a processingcircuit.

The terms “first,” “second,” “third,” and so forth, as used in theclaims, unless otherwise clear by context, is for clarity only anddoesn't otherwise indicate or imply any order in time. For instance, “afirst determination,” “a second determination,” and “a thirddetermination,” does not indicate or imply that the first determinationis to be made before the second determination, or vice versa, etc.

The illustrated embodiments of the embodiments herein can be alsopracticed in distributed computing environments where certain tasks areperformed by remote processing devices that are linked through acommunications network. In a distributed computing environment, programmodules can be located in both local and remote memory storage devices.

Computing devices typically comprise a variety of media, which cancomprise computer-readable storage media and/or communications media,which two terms are used herein differently from one another as follows.Computer-readable storage media can be any available storage media thatcan be accessed by the computer and comprises both volatile andnonvolatile media, removable and non-removable media. By way of example,and not limitation, computer-readable storage media can be implementedin connection with any method or technology for storage of informationsuch as computer-readable instructions, program modules, structured dataor unstructured data.

Computer-readable storage media can comprise, but are not limited to,random access memory (RAM), read only memory (ROM), electricallyerasable programmable read only memory (EEPROM), flash memory or othermemory technology, compact disk read only memory (CD-ROM), digitalversatile disk (DVD) or other optical disk storage, magnetic cassettes,magnetic tape, magnetic disk storage or other magnetic storage devicesor other tangible and/or non-transitory media which can be used to storedesired information. In this regard, the terms “tangible” or“non-transitory” herein as applied to storage, memory orcomputer-readable media, are to be understood to exclude onlypropagating transitory signals per se as modifiers and do not relinquishrights to all standard storage, memory or computer-readable media thatare not only propagating transitory signals per se.

Computer-readable storage media can be accessed by one or more local orremote computing devices, e.g., via access requests, queries or otherdata retrieval protocols, for a variety of operations with respect tothe information stored by the medium.

Communications media typically embody computer-readable instructions,data structures, program modules or other structured or unstructureddata in a data signal such as a modulated data signal, e.g., a carrierwave or other transport mechanism, and comprises any informationdelivery or transport media. The term “modulated data signal” or signalsrefers to a signal that has one or more of its characteristics set orchanged in such a manner as to encode information in one or moresignals. By way of example, and not limitation, communication mediacomprise wired media, such as a wired network or direct-wiredconnection, and wireless media such as acoustic, RF, infrared and otherwireless media.

With reference again to FIG. 46, the example environment 4600 fortransmitting and receiving signals via or forming at least part of abase station (e.g., base station devices 1504, macrocell site 1502, orbase stations 1614) or central office (e.g., central office 1501 or1611). At least a portion of the example environment 4600 can also beused for transmission devices 101 or 102. The example environment cancomprise a computer 4602, the computer 4602 comprising a processing unit4604, a system memory 4606 and a system bus 4608. The system bus 4608couple's system components including, but not limited to, the systemmemory 4606 to the processing unit 4604. The processing unit 4604 can beany of various commercially available processors. Dual microprocessorsand other multiprocessor architectures can also be employed as theprocessing unit 4604.

The system bus 4608 can be any of several types of bus structure thatcan further interconnect to a memory bus (with or without a memorycontroller), a peripheral bus, and a local bus using any of a variety ofcommercially available bus architectures. The system memory 4606comprises ROM 4610 and RAM 4612. A basic input/output system (BIOS) canbe stored in a non-volatile memory such as ROM, erasable programmableread only memory (EPROM), EEPROM, which BIOS contains the basic routinesthat help to transfer information between elements within the computer4602, such as during startup. The RAM 4612 can also comprise ahigh-speed RAM such as static RAM for caching data.

The computer 4602 further comprises an internal hard disk drive (HDD)4614 (e.g., EIDE (Enhanced Integrated Drive Electronics), SATA (SerialAdvanced Technology Attachment), which internal hard disk drive 4614 canalso be configured for external use in a suitable chassis (see 4614′), amagnetic floppy disk drive (FDD) 4616, (e.g., to read from or write to aremovable diskette 4618) and an optical disk drive 4620, (e.g., readinga CD-ROM disk 4622 or, to read from or write to other high capacityoptical media such as the DVD). The hard disk drive 4614, magnetic diskdrive 4616 and optical disk drive 4620 can be connected to the systembus 4608 by a hard disk drive interface 4624, a magnetic disk driveinterface 4626 and an optical drive interface 4628, respectively. Theinterface 4624 for external drive implementations comprises at least oneor both of Universal Serial Bus (USB) and Institute of Electrical andElectronics Engineers (IEEE) 1394 interface technologies. Other externaldrive connection technologies are within contemplation of theembodiments described herein.

The drives and their associated computer-readable storage media providenonvolatile storage of data, data structures, computer-executableinstructions, and so forth. For the computer 4602, the drives andstorage media accommodate the storage of any data in a suitable digitalformat. Although the description of computer-readable storage mediaabove refers to a hard disk drive (HDD), a removable magnetic diskette,and a removable optical media such as a CD or DVD, it should beappreciated by those skilled in the art that other types of storagemedia which are readable by a computer, such as zip drives, magneticcassettes, flash memory cards, cartridges, and the like, can also beused in the example operating environment, and further, that any suchstorage media can contain computer-executable instructions forperforming the methods described herein.

A number of program modules can be stored in the drives and RAM 4612,comprising an operating system 4630, one or more application programs4632, other program modules 4634 and program data 4636. All or portionsof the operating system, applications, modules, and/or data can also becached in the RAM 4612. The systems and methods described herein can beimplemented utilizing various commercially available operating systemsor combinations of operating systems. Examples of application programs4632 that can be implemented and otherwise executed by processing unit4604 include the diversity selection determining performed bytransmission device 101 or 102.

A user can enter commands and information into the computer 4602 throughone or more wired/wireless input devices, e.g., a keyboard 4638 and apointing device, such as a mouse 4640. Other input devices (not shown)can comprise a microphone, an infrared (IR) remote control, a joystick,a game pad, a stylus pen, touch screen or the like. These and otherinput devices are often wired/wireless connected to the processing unit4604 through an input device interface 4642 that can be coupled to thesystem bus 4608, but can be connected by other interfaces, such as aparallel port, an IEEE 1394 serial port, a game port, a universal serialbus (USB) port, an IR interface, etc.

A monitor 4644 or other type of display device can be also connected tothe system bus 4608 via an interface, such as a video adapter 4646. Itwill also be appreciated that in alternative embodiments, a monitor 4644can also be any display device (e.g., another computer having a display,a smart phone, a tablet computer, etc.) for receiving displayinformation associated with computer 4602 via any communication means,including via the Internet and cloud-based networks. In addition to themonitor 4644, a computer typically comprises other peripheral outputdevices (not shown), such as speakers, printers, etc.

The computer 4602 can operate in a networked environment using logicalconnections via wired and/or wireless communications to one or moreremote computers, such as a remote computer(s) 4648. The remotecomputer(s) 4648 can be a workstation, a server computer, a router, apersonal computer, portable computer, microprocessor-based entertainmentappliance, a peer device or other common network node, and typicallycomprises many or all of the elements described relative to the computer4602, although, for purposes of brevity, only a memory/storage device4650 is illustrated. The logical connections depicted comprisewired/wireless connectivity to a local area network (LAN) 4652 and/orlarger networks, e.g., a wide area network (WAN) 4654. Such LAN and WANnetworking environments are commonplace in offices and companies, andfacilitate enterprise-wide computer networks, such as intranets, all ofwhich can connect to a global communications network, e.g., theInternet.

When used in a LAN networking environment, the computer 4602 can beconnected to the local network 4652 through a wired and/or wirelesscommunication network interface or adapter 4656. The adapter 4656 canfacilitate wired or wireless communication to the LAN 4652, which canalso comprise a wireless AP (access point) disposed thereon forcommunicating with the wireless adapter 4656.

When used in a WAN networking environment, the computer 4602 cancomprise a modem 4658 or can be connected to a communications server onthe WAN 4654 or has other means for establishing communications over theWAN 4654, such as by way of the Internet. The modem 4658, which can beinternal or external and a wired or wireless device, can be connected tothe system bus 4608 via the input device interface 4642. In a networkedenvironment, program modules depicted relative to the computer 4602 orportions thereof, can be stored in the remote memory/storage device4650. It will be appreciated that the network connections shown areexample and other means of establishing a communications link betweenthe computers can be used.

The computer 4602 can be operable to communicate with any wirelessdevices or entities operatively disposed in wireless communication,e.g., a printer, scanner, desktop and/or portable computer, portabledata assistant, communications satellite, any piece of equipment orlocation associated with a wirelessly detectable tag (e.g., a kiosk,news stand, restroom), and telephone. This can comprise WirelessFidelity (Wi-Fi) and BLUETOOTH® wireless technologies. Thus, thecommunication can be a predefined structure as with a conventionalnetwork or simply an ad hoc communication between at least two devices.

Wi-Fi can allow connection to the Internet from a couch at home, a bedin a hotel room or a conference room at work, without wires. Wi-Fi is awireless technology similar to that used in a cell phone that enablessuch devices, e.g., computers, to send and receive data indoors and out;anywhere within the range of a base station. Wi-Fi networks use radiotechnologies called IEEE 802.11 (a, b, g, n, ac, ag etc.) to providesecure, reliable, fast wireless connectivity. A Wi-Fi network can beused to connect computers to each other, to the Internet, and to wirednetworks (which can use IEEE 802.3 or Ethernet). Wi-Fi networks operatein the unlicensed 2.4 and 5 GHz radio bands for example or with productsthat contain both bands (dual band), so the networks can providereal-world performance similar to the basic 10BaseT wired Ethernetnetworks used in many offices.

FIG. 47 presents an example embodiment 4700 of a mobile network platform4710 that can implement and exploit one or more aspects of the disclosedsubject matter described herein. In one or more embodiments, the mobilenetwork platform 4710 can generate and receive signals transmitted andreceived by base stations (e.g., base station devices 1504, macrocellsite 1502, or base stations 1614), central office (e.g., central office1501 or 1611), or transmission device 101 or 102 associated with thedisclosed subject matter. Generally, wireless network platform 4710 cancomprise components, e.g., nodes, gateways, interfaces, servers, ordisparate platforms, that facilitate both packet-switched (PS) (e.g.,internet protocol (IP), frame relay, asynchronous transfer mode (ATM))and circuit-switched (CS) traffic (e.g., voice and data), as well ascontrol generation for networked wireless telecommunication. As anon-limiting example, wireless network platform 4710 can be included intelecommunications carrier networks, and can be considered carrier-sidecomponents as discussed elsewhere herein. Mobile network platform 4710comprises CS gateway node(s) 4712 which can interface CS trafficreceived from legacy networks like telephony network(s) 4740 (e.g.,public switched telephone network (PSTN), or public land mobile network(PLMN)) or a signaling system #7 (SS7) network 4760. Circuit switchedgateway node(s) 4712 can authorize and authenticate traffic (e.g.,voice) arising from such networks. Additionally, CS gateway node(s) 4712can access mobility, or roaming, data generated through SS7 network4760; for instance, mobility data stored in a visited location register(VLR), which can reside in memory 4730. Moreover, CS gateway node(s)4712 interfaces CS-based traffic and signaling and PS gateway node(s)4718. As an example, in a 3GPP (3rd generation Partnership Project) UMTS(Universal Mobile Telecommunications Service) network, CS gatewaynode(s) 4712 can be realized at least in part in gateway GPRS (GeneralPacket Radio Services) support node(s) (GGSN). It should be appreciatedthat functionality and specific operation of CS gateway node(s) 4712, PSgateway node(s) 4718, and serving node(s) 4716, is provided and dictatedby radio technology(ies) utilized by mobile network platform 4710 fortelecommunication.

In addition to receiving and processing CS-switched traffic andsignaling, PS gateway node(s) 4718 can authorize and authenticatePS-based data sessions with served mobile devices. Data sessions cancomprise traffic, or content(s), exchanged with networks external to thewireless network platform 4710, like wide area network(s) (WANs) 4750,enterprise network(s) 4770, and service network(s) 4780, which can beembodied in local area network(s) (LANs), can also be interfaced withmobile network platform 4710 through PS gateway node(s) 4718. It is tobe noted that WANs 4750 and enterprise network(s) 4760 can embody, atleast in part, a service network(s) like IP multimedia subsystem (IMS).Based on radio technology layer(s) available in technology resource(s),packet-switched gateway node(s) 4718 can generate packet data protocolcontexts when a data session is established; other data structures thatfacilitate routing of packetized data also can be generated. To thatend, in an aspect, PS gateway node(s) 4718 can comprise a tunnelinterface (e.g., tunnel termination gateway (TTG) in 3GPP UMTSnetwork(s) (not shown)) which can facilitate packetized communicationwith disparate wireless network(s), such as Wi-Fi networks.

In embodiment 4700, wireless network platform 4710 also comprisesserving node(s) 4716 that, based upon available radio technologylayer(s) within technology resource(s), convey the various packetizedflows of data streams received through PS gateway node(s) 4718. It is tobe noted that for technology resource(s) that rely primarily on CScommunication, server node(s) can deliver traffic without reliance on PSgateway node(s) 4718; for example, server node(s) can embody at least inpart a mobile switching center. As an example, in a 3GPP UMTS network,serving node(s) 4716 can be embodied in serving GPRS support node(s)(SGSN).

For radio technologies that exploit packetized communication, server(s)4714 in wireless network platform 4710 can execute numerous applicationsthat can generate multiple disparate packetized data streams or flows,and manage (e.g., schedule, queue, format . . . ) such flows. Suchapplication(s) can comprise add-on features to standard services (forexample, provisioning, billing, customer support . . . ) provided bywireless network platform 4710. Data streams (e.g., content(s) that arepart of a voice call or data session) can be conveyed to PS gatewaynode(s) 4718 for authorization/authentication and initiation of a datasession, and to serving node(s) 4716 for communication thereafter. Inaddition to application server, server(s) 4714 can comprise utilityserver(s), a utility server can comprise a provisioning server, anoperations and maintenance server, a security server that can implementat least in part a certificate authority and firewalls as well as othersecurity mechanisms, and the like. In an aspect, security server(s)secure communication served through wireless network platform 4710 toensure network's operation and data integrity in addition toauthorization and authentication procedures that CS gateway node(s) 4712and PS gateway node(s) 4718 can enact. Moreover, provisioning server(s)can provision services from external network(s) like networks operatedby a disparate service provider; for instance, WAN 4750 or GlobalPositioning System (GPS) network(s) (not shown). Provisioning server(s)can also provision coverage through networks associated to wirelessnetwork platform 4710 (e.g., deployed and operated by the same serviceprovider), such as the distributed antennas networks shown in FIG. 1that enhance wireless service coverage by providing more networkcoverage. Repeater devices such as those shown in FIGS. 7, 8, and 9A, 9Balso improve network coverage in order to enhance subscriber serviceexperience by way of UE 4775 (which, as shown for example in FIG. 47,can be in bidirectional communication with Mobile Network Platform 4710via RAN (radio access network)).

It is to be noted that server(s) 4714 can comprise one or moreprocessors configured to confer at least in part the functionality ofmacro network platform 4710. To that end, the one or more processor canexecute code instructions stored in memory 4730, for example. It isshould be appreciated that server(s) 4714 can comprise a contentmanager, which operates in substantially the same manner as describedhereinbefore.

In example embodiment 4700, memory 4730 can store information related tooperation of wireless network platform 4710. Other operationalinformation can comprise provisioning information of mobile devicesserved through wireless platform network 4710, subscriber databases;application intelligence, pricing schemes, e.g., promotional rates,flat-rate programs, couponing campaigns; technical specification(s)consistent with telecommunication protocols for operation of disparateradio, or wireless, technology layers; and so forth. Memory 4730 canalso store information from at least one of telephony network(s) 4740,WAN 4750, enterprise network(s) 4770, or SS7 network 4760. In an aspect,memory 4730 can be, for example, accessed as part of a data storecomponent or as a remotely connected memory store.

In order to provide a context for the various aspects of the disclosedsubject matter, FIG. 47, and the following discussion, are intended toprovide a brief, general description of a suitable environment in whichthe various aspects of the disclosed subject matter can be implemented.While the subject matter has been described above in the general contextof computer-executable instructions of a computer program that runs on acomputer and/or computers, those skilled in the art will recognize thatthe disclosed subject matter also can be implemented in combination withother program modules. Generally, program modules comprise routines,programs, components, data structures, etc. that perform particulartasks and/or implement particular abstract data types.

FIG. 48 depicts an illustrative embodiment of a communication device4800. The communication device 4800 can serve as an illustrativeembodiment of devices such as mobile devices and in-building devicesreferred to by the subject disclosure (e.g., in FIGS. 15, 16A and 16B).

The communication device 4800 can comprise a wireline and/or wirelesstransceiver 4802 (herein transceiver 4802), a user interface (UI) 4804,a power supply 4814, a location receiver 4816, a motion sensor 4818, anorientation sensor 4820, and a controller 4806 for managing operationsthereof. The transceiver 4802 can support short-range or long-rangewireless access technologies such as BLUETOOTH®, ZIGBEE®, WiFi, DECT(Digital Enhanced Cordless Telecommunications), or cellularcommunication technologies, just to mention a few (BLUETOOTH® andZIGBEE® are trademarks registered by the BLUETOOTH® Special InterestGroup and the ZIGBEE® Alliance, respectively). Cellular technologies caninclude, for example, CDMA-1X (Code Division Multiple Access),UMTS/HSDPA (Universal Mobile Telecommunications Service/High-SpeedDownlink Packet Access), GSM/GPRS (Global System for MobileCommunications/General Packet Radio Services), TDMA/EDGE (Time-divisionmultiple access/Enhanced GPRS), EV/DO (Evolution-Data Optimized), WiMAX(Worldwide Interoperability for Microwave Access), SDR (Software-definedradio), LTE (Long-Term Evolution), as well as other next generationwireless communication technologies as they arise. The transceiver 4802can also be adapted to support circuit-switched wireline accesstechnologies (such as PSTN), packet-switched wireline accesstechnologies (such as TCP/IP, VoIP, etc.), and combinations thereof.

The UI 4804 (User Interface) can include a depressible ortouch-sensitive keypad 4808 with a navigation mechanism such as a rollerball, a joystick, a mouse, or a navigation disk for manipulatingoperations of the communication device 4800. The keypad 4808 can be anintegral part of a housing assembly of the communication device 4800 oran independent device operably coupled thereto by a tethered wirelineinterface (such as a USB cable) or a wireless interface supporting forexample BLUETOOTH®. The keypad 4808 can represent a numeric keypadcommonly used by phones, and/or a QWERTY keypad with alphanumeric keys.The UI 4804 can further include a display 4810 such as monochrome orcolor LCD (Liquid Crystal Display), OLED (Organic Light Emitting Diode)or other suitable display technology for conveying images to an end userof the communication device 4800. In an embodiment where the display4810 is touch-sensitive, a portion or all of the keypad 4808 can bepresented by way of the display 4810 with navigation features.

The display 4810 can use touch screen technology to also serve as a userinterface for detecting user input. As a touch screen display, thecommunication device 4800 can be adapted to present a user interfacehaving graphical user interface (GUI) elements that can be selected by auser with a touch of a finger. The touch screen display 4810 can beequipped with capacitive, resistive or other forms of sensing technologyto detect how much surface area of a user's finger has been placed on aportion of the touch screen display. This sensing information can beused to control the manipulation of the GUI elements or other functionsof the user interface. The display 4810 can be an integral part of thehousing assembly of the communication device 4800 or an independentdevice communicatively coupled thereto by a tethered wireline interface(such as a cable) or a wireless interface.

The UI 4804 can also include an audio system 4812 that utilizes audiotechnology for conveying low volume audio (such as audio heard inproximity of a human ear) and high volume audio (such as speakerphonefor hands free operation). The audio system 4812 can further include amicrophone for receiving audible signals of an end user. The audiosystem 4812 can also be used for voice recognition applications. The UI4804 can further include an image sensor 4813 such as a charged coupleddevice (CCD) camera for capturing still or moving images.

The power supply 4814 can utilize common power management technologiessuch as replaceable and rechargeable batteries, supply regulationtechnologies, and/or charging system technologies for supplying energyto the components of the communication device 4800 to facilitatelong-range or short-range portable communications. Alternatively, or incombination, the charging system can utilize external power sources suchas DC power supplied over a physical interface such as a USB port orother suitable tethering technologies.

The location receiver 4816 can utilize location technology such as aglobal positioning system (GPS) receiver capable of assisted GPS foridentifying a location of the communication device 4800 based on signalsgenerated by a constellation of GPS satellites, which can be used forfacilitating location services such as navigation. The motion sensor4818 can utilize motion sensing technology such as an accelerometer, agyroscope, or other suitable motion sensing technology to detect motionof the communication device 4800 in three-dimensional space. Theorientation sensor 4820 can utilize orientation sensing technology suchas a magnetometer to detect the orientation of the communication device4800 (north, south, west, and east, as well as combined orientations indegrees, minutes, or other suitable orientation metrics).

The communication device 4800 can use the transceiver 4802 to alsodetermine a proximity to a cellular, WiFi, BLUETOOTH®, or other wirelessaccess points by sensing techniques such as utilizing a received signalstrength indicator (RSSI) and/or signal time of arrival (TOA) or time offlight (TOF) measurements. The controller 4806 can utilize computingtechnologies such as a microprocessor, a digital signal processor (DSP),programmable gate arrays, application specific integrated circuits,and/or a video processor with associated storage memory such as Flash,ROM, RAM, SRAM, DRAM or other storage technologies for executingcomputer instructions, controlling, and processing data supplied by theaforementioned components of the communication device 4800.

Other components not shown in FIG. 48 can be used in one or moreembodiments of the subject disclosure. For instance, the communicationdevice 4800 can include a slot for adding or removing an identity modulesuch as a Subscriber Identity Module (SIM) card or Universal IntegratedCircuit Card (UICC). SIM or UICC cards can be used for identifyingsubscriber services, executing programs, storing subscriber data, and soon.

In the subject specification, terms such as “store,” “storage,” “datastore,” data storage,” “database,” and substantially any otherinformation storage component relevant to operation and functionality ofa component, refer to “memory components,” or entities embodied in a“memory” or components comprising the memory. It will be appreciatedthat the memory components described herein can be either volatilememory or nonvolatile memory, or can comprise both volatile andnonvolatile memory, by way of illustration, and not limitation, volatilememory, non-volatile memory, disk storage, and memory storage. Further,nonvolatile memory can be included in read only memory (ROM),programmable ROM (PROM), electrically programmable ROM (EPROM),electrically erasable ROM (EEPROM), or flash memory. Volatile memory cancomprise random access memory (RAM), which acts as external cachememory. By way of illustration and not limitation, RAM is available inmany forms such as synchronous RAM (SRAM), dynamic RAM (DRAM),synchronous DRAM (SDRAM), double data rate SDRAM (DDR SDRAM), enhancedSDRAM (ESDRAM), Synchlink DRAM (SLDRAM), and direct Rambus RAM (DRRAM).Additionally, the disclosed memory components of systems or methodsherein are intended to comprise, without being limited to comprising,these and any other suitable types of memory.

Moreover, it will be noted that the disclosed subject matter can bepracticed with other computer system configurations, comprisingsingle-processor or multiprocessor computer systems, mini-computingdevices, mainframe computers, as well as personal computers, hand-heldcomputing devices (e.g., PDA, phone, smartphone, watch, tabletcomputers, netbook computers, etc.), microprocessor-based orprogrammable consumer or industrial electronics, and the like. Theillustrated aspects can also be practiced in distributed computingenvironments where tasks are performed by remote processing devices thatare linked through a communications network; however, some if not allaspects of the subject disclosure can be practiced on stand-alonecomputers. In a distributed computing environment, program modules canbe located in both local and remote memory storage devices.

Some of the embodiments described herein can also employ artificialintelligence (AI) to facilitate automating one or more featuresdescribed herein. For example, artificial intelligence can be used inoptional training controller 230 evaluate and select candidatefrequencies, modulation schemes, MIMO modes, and/or guided wave modes inorder to maximize transfer efficiency. The embodiments (e.g., inconnection with automatically identifying acquired cell sites thatprovide a maximum value/benefit after addition to an existingcommunication network) can employ various AI-based schemes for carryingout various embodiments thereof. Moreover, the classifier can beemployed to determine a ranking or priority of the each cell site of theacquired network. A classifier is a function that maps an inputattribute vector, x=(x1, x2, x3, x4, . . . , xn), to a confidence thatthe input belongs to a class, that is, f(x)=confidence (class). Suchclassification can employ a probabilistic and/or statistical-basedanalysis (e.g., factoring into the analysis utilities and costs) toprognose or infer an action that a user desires to be automaticallyperformed. A support vector machine (SVM) is an example of a classifierthat can be employed. The SVM operates by finding a hypersurface in thespace of possible inputs, which the hypersurface attempts to split thetriggering criteria from the non-triggering events. Intuitively, thismakes the classification correct for testing data that is near, but notidentical to training data. Other directed and undirected modelclassification approaches comprise, e.g., naïve Bayes, Bayesiannetworks, decision trees, neural networks, fuzzy logic models, andprobabilistic classification models providing different patterns ofindependence can be employed. Classification as used herein also isinclusive of statistical regression that is utilized to develop modelsof priority.

As will be readily appreciated, one or more of the embodiments canemploy classifiers that are explicitly trained (e.g., via a generictraining data) as well as implicitly trained (e.g., via observing UEbehavior, operator preferences, historical information, receivingextrinsic information). For example, SVMs can be configured via alearning or training phase within a classifier constructor and featureselection module. Thus, the classifier(s) can be used to automaticallylearn and perform a number of functions, including but not limited todetermining according to a predetermined criteria which of the acquiredcell sites will benefit a maximum number of subscribers and/or which ofthe acquired cell sites will add minimum value to the existingcommunication network coverage, etc.

As used in some contexts in this application, in some embodiments, theterms “component,” “system” and the like are intended to refer to, orcomprise, a computer-related entity or an entity related to anoperational apparatus with one or more specific functionalities, whereinthe entity can be either hardware, a combination of hardware andsoftware, software, or software in execution. As an example, a componentmay be, but is not limited to being, a process running on a processor, aprocessor, an object, an executable, a thread of execution,computer-executable instructions, a program, and/or a computer. By wayof illustration and not limitation, both an application running on aserver and the server can be a component. One or more components mayreside within a process and/or thread of execution and a component maybe localized on one computer and/or distributed between two or morecomputers. In addition, these components can execute from variouscomputer readable media having various data structures stored thereon.The components may communicate via local and/or remote processes such asin accordance with a signal having one or more data packets (e.g., datafrom one component interacting with another component in a local system,distributed system, and/or across a network such as the Internet withother systems via the signal). As another example, a component can be anapparatus with specific functionality provided by mechanical partsoperated by electric or electronic circuitry, which is operated by asoftware or firmware application executed by a processor, wherein theprocessor can be internal or external to the apparatus and executes atleast a part of the software or firmware application. As yet anotherexample, a component can be an apparatus that provides specificfunctionality through electronic components without mechanical parts,the electronic components can comprise a processor therein to executesoftware or firmware that confers at least in part the functionality ofthe electronic components. While various components have beenillustrated as separate components, it will be appreciated that multiplecomponents can be implemented as a single component, or a singlecomponent can be implemented as multiple components, without departingfrom example embodiments.

Further, the various embodiments can be implemented as a method,apparatus or article of manufacture using standard programming and/orengineering techniques to produce software, firmware, hardware or anycombination thereof to control a computer to implement the disclosedsubject matter. The term “article of manufacture” as used herein isintended to encompass a computer program accessible from anycomputer-readable device or computer-readable storage/communicationsmedia. For example, computer readable storage media can include, but arenot limited to, magnetic storage devices (e.g., hard disk, floppy disk,magnetic strips), optical disks (e.g., compact disk (CD), digitalversatile disk (DVD)), smart cards, and flash memory devices (e.g.,card, stick, key drive). Of course, those skilled in the art willrecognize many modifications can be made to this configuration withoutdeparting from the scope or spirit of the various embodiments.

In addition, the words “example” and “exemplary” are used herein to meanserving as an instance or illustration. Any embodiment or designdescribed herein as “example” or “exemplary” is not necessarily to beconstrued as preferred or advantageous over other embodiments ordesigns. Rather, use of the word example or exemplary is intended topresent concepts in a concrete fashion. As used in this application, theterm “or” is intended to mean an inclusive “or” rather than an exclusive“or”. That is, unless specified otherwise or clear from context, “Xemploys A or B” is intended to mean any of the natural inclusivepermutations. That is, if X employs A; X employs B; or X employs both Aand B, then “X employs A or B” is satisfied under any of the foregoinginstances. In addition, the articles “a” and “an” as used in thisapplication and the appended claims should generally be construed tomean “one or more” unless specified otherwise or clear from context tobe directed to a singular form.

Moreover, terms such as “user equipment,” “mobile station,” “mobile,”subscriber station,” “access terminal,” “terminal,” “handset,” “mobiledevice” (and/or terms representing similar terminology) can refer to awireless device utilized by a subscriber or user of a wirelesscommunication service to receive or convey data, control, voice, video,sound, gaming or substantially any data-stream or signaling-stream. Theforegoing terms are utilized interchangeably herein and with referenceto the related drawings.

Furthermore, the terms “user,” “subscriber,” “customer,” “consumer” andthe like are employed interchangeably throughout, unless contextwarrants particular distinctions among the terms. It should beappreciated that such terms can refer to human entities or automatedcomponents supported through artificial intelligence (e.g., a capacityto make inference based, at least, on complex mathematical formalisms),which can provide simulated vision, sound recognition and so forth.

As employed herein, the term “processor” can refer to substantially anycomputing processing unit or device comprising, but not limited tocomprising, single-core processors; single-processors with softwaremultithread execution capability; multi-core processors; multi-coreprocessors with software multithread execution capability; multi-coreprocessors with hardware multithread technology; parallel platforms; andparallel platforms with distributed shared memory. Additionally, aprocessor can refer to an integrated circuit, an application specificintegrated circuit (ASIC), a digital signal processor (DSP), a fieldprogrammable gate array (FPGA), a programmable logic controller (PLC), acomplex programmable logic device (CPLD), a discrete gate or transistorlogic, discrete hardware components or any combination thereof designedto perform the functions described herein. Processors can exploitnano-scale architectures such as, but not limited to, molecular andquantum-dot based transistors, switches and gates, in order to optimizespace usage or enhance performance of user equipment. A processor canalso be implemented as a combination of computing processing units.

As used herein, terms such as “data storage,” data storage,” “database,”and substantially any other information storage component relevant tooperation and functionality of a component, refer to “memorycomponents,” or entities embodied in a “memory” or components comprisingthe memory. It will be appreciated that the memory components orcomputer-readable storage media, described herein can be either volatilememory or nonvolatile memory or can include both volatile andnonvolatile memory.

What has been described above includes mere examples of variousembodiments. It is, of course, not possible to describe everyconceivable combination of components or methodologies for purposes ofdescribing these examples, but one of ordinary skill in the art canrecognize that many further combinations and permutations of the presentembodiments are possible. Accordingly, the embodiments disclosed and/orclaimed herein are intended to embrace all such alterations,modifications and variations that fall within the spirit and scope ofthe appended claims. Furthermore, to the extent that the term “includes”is used in either the detailed description or the claims, such term isintended to be inclusive in a manner similar to the term “comprising” as“comprising” is interpreted when employed as a transitional word in aclaim.

In addition, a flow diagram may include a “start” and/or “continue”indication. The “start” and “continue” indications reflect that thesteps presented can optionally be incorporated in or otherwise used inconjunction with other routines. In this context, “start” indicates thebeginning of the first step presented and may be preceded by otheractivities not specifically shown. Further, the “continue” indicationreflects that the steps presented may be performed multiple times and/ormay be succeeded by other activities not specifically shown. Further,while a flow diagram indicates a particular ordering of steps, otherorderings are likewise possible provided that the principles ofcausality are maintained.

As may also be used herein, the term(s) “operably coupled to”, “coupledto”, and/or “coupling” includes direct coupling between items and/orindirect coupling between items via one or more intervening items. Suchitems and intervening items include, but are not limited to, junctions,communication paths, components, circuit elements, circuits, functionalblocks, and/or devices. As an example of indirect coupling, a signalconveyed from a first item to a second item may be modified by one ormore intervening items by modifying the form, nature or format ofinformation in a signal, while one or more elements of the informationin the signal are nevertheless conveyed in a manner than can berecognized by the second item. In a further example of indirectcoupling, an action in a first item can cause a reaction on the seconditem, as a result of actions and/or reactions in one or more interveningitems.

Although specific embodiments have been illustrated and describedherein, it should be appreciated that any arrangement which achieves thesame or similar purpose may be substituted for the embodiments describedor shown by the subject disclosure. The subject disclosure is intendedto cover any and all adaptations or variations of various embodiments.Combinations of the above embodiments, and other embodiments notspecifically described herein, can be used in the subject disclosure.For instance, one or more features from one or more embodiments can becombined with one or more features of one or more other embodiments. Inone or more embodiments, features that are positively recited can alsobe negatively recited and excluded from the embodiment with or withoutreplacement by another structural and/or functional feature. The stepsor functions described with respect to the embodiments of the subjectdisclosure can be performed in any order. The steps or functionsdescribed with respect to the embodiments of the subject disclosure canbe performed alone or in combination with other steps or functions ofthe subject disclosure, as well as from other embodiments or from othersteps that have not been described in the subject disclosure. Further,more than or less than all of the features described with respect to anembodiment can also be utilized.

What is claimed is:
 1. A communication device, comprising: a dielectricantenna having a dielectric lens and a dielectric body; and a dielectricfeedline coupled to the dielectric antenna at a second endpoint of thedielectric feedline, a first endpoint of the dielectric feedlinecomprising a conical structure that facilitates reducing a reflection,at the first endpoint, of first electromagnetic waves directed to thedielectric feedline, the first electromagnetic waves being guided alongthe dielectric feedline without requiring an electrical return path, andthe first electromagnetic waves propagating through the dielectric bodyto the dielectric lens to generate near-field wireless signals.
 2. Thecommunication device of claim 1, wherein the first electromagnetic wavesare generated via a port of a transmitter.
 3. The communication deviceof claim 2, wherein the port of the transmitter comprises an opening ofa hollow waveguide.
 4. The communication device of claim 3, wherein thefirst endpoint of the dielectric feedline protrudes into the opening ofthe hollow waveguide.
 5. The communication device of claim 4, wherein aportion of the opening of the hollow waveguide comprises an innerthreaded surface that enables an adjustment of a position of the firstendpoint of the dielectric feedline within the hollow waveguide.
 6. Thecommunication device of claim 4, further comprising an electromechanicaldevice that facilitates an adjustment of a longitudinal position of thefirst endpoint of the dielectric feedline within the hollow waveguide.7. The communication device of claim 6, further comprising a processorthat facilitates a determination of a target position of the firstendpoint of the dielectric feedline within the hollow waveguide thatachieves a desired coupling of the first electromagnetic waves onto thedielectric feedline.
 8. The communication device of claim 7, wherein theprocessor is coupled to the electromechanical device, and wherein theprocessor facilitates directing the electromechanical device to adjustthe longitudinal position of the first endpoint of the dielectricfeedline within the hollow waveguide to the target position.
 9. Thecommunication device of claim 1, further comprising a collar, whereinthe collar includes a first opening and a second opening thatfacilitates adjusting a proximity between a port of a transmitter to thefirst endpoint of the dielectric feedline.
 10. The communication deviceof claim 1, wherein a receiver is coupled to the dielectric feedline andfacilitates receiving second electromagnetic waves guided by thedielectric feedline, and wherein the second electromagnetic waves aregenerated from second wireless signals received by an aperture of thedielectric antenna.
 11. An antenna structure, comprising: a dielectricantenna having a dielectric lens and a dielectric body; and a feedlinecoupled to the dielectric antenna at a second endpoint of the feedline,a first endpoint of the feedline being configured, via use of a pointedstructure, to reduce a reflection at the first endpoint ofelectromagnetic waves directed to the feedline, the electromagneticwaves being guided along the feedline without requiring an electricalreturn path, and the electromagnetic waves propagating through thedielectric body to the dielectric lens to generate wireless signals. 12.The antenna structure of claim 11, wherein the pointed structurecomprises a conical structure.
 13. The antenna structure of claim 12,wherein the electromagnetic waves are generated by a port of atransmitter.
 14. The antenna structure of claim 13, wherein a proximitybetween the port of the transmitter and the feedline is adjustable. 15.A method, comprising: aligning a feedline of a dielectric antennacomprising a dielectric lens and a dielectric body with a port of awaveguide system; and transmitting, by the waveguide system, firstelectromagnetic waves that are guided along the feedline withoutrequiring an electrical return path, the first electromagnetic wavespropagating along the feedline and through the dielectric body to thedielectric lens to generate first wireless signals, an endpoint of thefeedline comprising a pointed structure that facilitates reducing areflection at the endpoint of the first electromagnetic waves from theport of the waveguide system.
 16. The method of claim 15, wherein thealigning comprises longitudinal adjustment of the feedline.
 17. Themethod of claim 16, wherein the longitudinal adjustment of the feedlineis relative to the port of the waveguide system.
 18. The method of claim17, wherein the port of the waveguide system comprises a hollow opening.19. The method of claim 15, wherein the pointed structure comprises aconical endpoint.
 20. The method of claim 15, further comprisingreceiving, by the waveguide system, second electromagnetic waves via thefeedline, wherein second wireless signals are converted into the secondelectromagnetic waves by the dielectric lens, and wherein the secondelectromagnetic waves propagate from the dielectric lens through thedielectric body of the dielectric antenna to the feedline.